Method and apparatus for synchronization signal design

ABSTRACT

A method of a base station (BS) for transmitting synchronization signals in a wireless communication system. The method comprises generating a primary synchronization signal (PSS) including one of multiple PSS sequences that is generated based on a M-sequence of length 127 in a frequency domain, wherein the PSS indicates part of cell identification (ID) information using a cyclic shift performed on the M-sequence generating the PSS; generating a secondary synchronization signal (SSS) including one of multiple SSS sequences that is generated based on multiple BPSK modulated M-sequences of length 127 in the frequency domain, wherein the SSS indicates the cell ID information using cyclic shifts performed on the M-sequences generating the SSS; and transmitting, to a user equipment (UE), the PSS and SSS over downlink channels.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/788,136, filed Feb. 11, 2020, which is a continuation of U.S. patentapplication Ser. No. 16/544,143, filed Aug. 19, 2019, which is acontinuation of U.S. patent application Ser. No. 15/796,558, filed Oct.27, 2017, now U.S. Pat. No. 10,389,567, which claims priority to U.S.Provisional Patent Application No. 62/417,069, filed Nov. 3, 2016; U.S.Provisional Patent Application No. 62/420,961, filed Nov. 11, 2016; U.S.Provisional Patent Application No. 62/428,633, filed Dec. 1, 2016; U.S.Provisional Patent Application No. 62/432,360, filed Dec. 9, 2016; U.S.Provisional Patent Application No. 62/450,756, filed Jan. 26, 2017; U.S.Provisional Patent Application No. 62/458,787, filed Feb. 14, 2017; U.S.Provisional Patent Application No. 62/463,295, filed Feb. 24, 2017; U.S.Provisional Patent Application No. 62/466,771, filed Mar. 3, 2017; U.S.Provisional Patent Application No. 62/482,423, filed Apr. 6, 2017; U.S.Provisional Patent Application No. 62/506,848, filed May 16, 2017; andU.S. Provisional Patent Application No. 62/552,750, filed Aug. 31, 2017.The content of the above-identified patent documents are incorporatedherein by reference.

TECHNICAL FIELD

The present application relates generally to synchronization signaldesign. More specifically, this disclosure relates to NR-SS sequencedesign in an advanced wireless communication system.

BACKGROUND

In a wireless communication network, a network access and a radioresource management (RRM) are enabled by physical layer synchronizationsignals and higher (MAC) layer procedures. In particular, a UE attemptsto detect the presence of synchronization signals along with at leastone cell identification (ID) for initial access. Once the UE is in thenetwork and associated with a serving cell, the UE monitors severalneighboring cells by attempting to detect their synchronization signalsand/or measuring the associated cell-specific reference signals (RSs).For next generation cellular systems such as third generationpartnership-new radio access or interface (3GPP-NR), efficient andunified radio resource acquisition or tracking mechanism which works forvarious use cases such as enhanced mobile broadband (eMBB), ultrareliable low latency (URLLC), massive machine type communication (mMTC),each corresponding to a different coverage requirement and frequencybands with different propagation losses is desirable. Most likelydesigned with a different network and radio resource paradigm, seamlessand low-latency RRM is also desirable.

SUMMARY

Embodiments of the present disclosure provide a synchronization signaldesign in an advanced wireless communication system.

In one embodiment, a base station (BS) for transmitting synchronizationsignals in a wireless communication system is provided. The BS comprisesat least one processor configured to generate a primary synchronizationsignal (PSS) including one of multiple PSS sequences that is generatedbased on a M-sequence of length 127 in a frequency domain, wherein thePSS includes part of cell identification (ID) information using a cyclicshift performed on the M-sequence generating the PSS; and generate asecondary synchronization signal (SSS) including one of multiple SSSsequences that is generated based on multiple M-sequences of length 127in the frequency domain, wherein the SSS includes the cellidentification (ID) information using cyclic shift performed on themultiple M-sequence generating the SSS. The BS further comprises atransceiver configured to transmit, to a user equipment (UE), the PSSand the SSS over downlink channels.

In another embodiment, a method of a base station (BS) for transmittingsynchronization signals in a wireless communication system is provided.The method comprises generating a primary synchronization signal (PSS)including one of multiple PSS sequences that is generated based on aM-sequence of length 127 in a frequency domain, wherein the PSS includespart of cell identification (ID) information using a cyclic shiftperformed on the M-sequence generating the PSS; generating a secondarysynchronization signal (SSS) including one of multiple SSS sequencesthat is generated based on multiple M-sequences of length 127 in thefrequency domain, wherein the SSS indicates the cell identification (ID)information using cyclic shifts performed on the multiple M-sequencesgenerating the SSS; and transmitting, to a user equipment (UE), the PSSand SSS over downlink channels.

In yet another embodiment, a user equipment (UE) for transmittingsynchronization signals in a wireless communication system is provided.The UE comprises a transceiver configured to receive and detect, from abase station (BS), a primary synchronization signal (PSS) and asecondary synchronization signal (SSS) over downlink channels. The UEfurther comprises at least one processor configured to determine the PSSincluding one of multiple PSS sequences that is generated based on aM-sequence of length 127 in a frequency domain, wherein the PSS includespart of cell identification (ID) information using a cyclic shiftperformed on the M-sequence generating the PSS; and determine the SSSincluding one of multiple SSS sequences that is generated based onmultiple M-sequences of length-127 in the frequency domain, wherein theSSS indicates the cell identification (ID) information using cyclicshifts performed on the multiple M-sequences generating the SSS.

Other technical features may be readily apparent to one skilled in theart from the following figures, descriptions, and claims.

Before undertaking the DETAILED DESCRIPTION below, it may beadvantageous to set forth definitions of certain words and phrases usedthroughout this patent document. The term “couple” and its derivativesrefer to any direct or indirect communication between two or moreelements, whether or not those elements are in physical contact with oneanother. The terms “transmit,” “receive,” and “communicate,” as well asderivatives thereof, encompass both direct and indirect communication.The terms “include” and “comprise,” as well as derivatives thereof, meaninclusion without limitation. The term “or” is inclusive, meaningand/or. The phrase “associated with,” as well as derivatives thereof,means to include, be included within, interconnect with, contain, becontained within, connect to or with, couple to or with, be communicablewith, cooperate with, interleave, juxtapose, be proximate to, be boundto or with, have, have a property of, have a relationship to or with, orthe like. The term “controller” means any device, system or part thereofthat controls at least one operation. Such a controller may beimplemented in hardware or a combination of hardware and software and/orfirmware. The functionality associated with any particular controllermay be centralized or distributed, whether locally or remotely. Thephrase “at least one of,” when used with a list of items, means thatdifferent combinations of one or more of the listed items may be used,and only one item in the list may be needed. For example, “at least oneof: A, B, and C” includes any of the following combinations: A, B, C, Aand B, A and C, B and C, and A and B and C.

Moreover, various functions described below can be implemented orsupported by one or more computer programs, each of which is formed fromcomputer readable program code and embodied in a computer readablemedium. The terms “application” and “program” refer to one or morecomputer programs, software components, sets of instructions,procedures, functions, objects, classes, instances, related data, or aportion thereof adapted for implementation in a suitable computerreadable program code. The phrase “computer readable program code”includes any type of computer code, including source code, object code,and executable code. The phrase “computer readable medium” includes anytype of medium capable of being accessed by a computer, such as readonly memory (ROM), random access memory (RAM), a hard disk drive, acompact disc (CD), a digital video disc (DVD), or any other type ofmemory. A “non-transitory” computer readable medium excludes wired,wireless, optical, or other communication links that transporttransitory electrical or other signals. A non-transitory computerreadable medium includes media where data can be permanently stored andmedia where data can be stored and later overwritten, such as arewritable optical disc or an erasable memory device.

Definitions for other certain words and phrases are provided throughoutthis patent document. Those of ordinary skill in the art shouldunderstand that in many if not most instances, such definitions apply toprior as well as future uses of such defined words and phrases.

BRIEF DESCRIPTION OF THE DRAWINGS

For a more complete understanding of the present disclosure and itsadvantages, reference is now made to the following description taken inconjunction with the accompanying drawings, in which like referencenumerals represent like parts:

FIG. 1 illustrates an example wireless network according to embodimentsof the present disclosure;

FIG. 2 illustrates an example eNB according to embodiments of thepresent disclosure;

FIG. 3 illustrates an example UE according to embodiments of the presentdisclosure;

FIG. 4A illustrates a high-level diagram of an orthogonal frequencydivision multiple access transmit path according to embodiments of thepresent disclosure;

FIG. 4B illustrates a high-level diagram of an orthogonal frequencydivision multiple access receive path according to embodiments of thepresent disclosure;

FIG. 5 illustrates a transmitter block diagram for a PDSCH in a subframeaccording to embodiments of the present disclosure;

FIG. 6 illustrates a receiver block diagram for a PDSCH in a subframeaccording to embodiments of the present disclosure;

FIG. 7 illustrates a transmitter block diagram for a PUSCH in a subframeaccording to embodiments of the present disclosure;

FIG. 8 illustrates a receiver block diagram for a PUSCH in a subframeaccording to embodiments of the present disclosure;

FIG. 9 illustrates an example multiplexing of two slices according toembodiments of the present disclosure;

FIG. 10 illustrates an example antenna blocks according to embodimentsof the present disclosure;

FIG. 11 illustrates an example UE mobility scenario according toembodiments of the present disclosure;

FIG. 12 illustrates an example beam sweeping operation according toembodiments of the present disclosure;

FIG. 13 illustrates an example SS burst including an SS block accordingto embodiments of the present disclosure;

FIG. 14 illustrates an example SS burst including multiplenon-successive SS blocks according to embodiments of the presentdisclosure;

FIG. 15 illustrates an example SS burst including multiple successive SSblocks according to embodiments of the present disclosure;

FIG. 16 illustrates another example SS burst including multiplesuccessive SS blocks according to embodiments of the present disclosure;

FIG. 17 illustrates a flow chart of NR-SSS construction according toembodiments of the present disclosure;

FIG. 18A illustrates an example combination of mapping and multiplexingaccording to embodiments of the present disclosure;

FIG. 18B illustrates another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 18C illustrates yet another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 19A illustrates yet another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 19B illustrates yet another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 19C illustrates yet another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 20 illustrates yet another example combination of mapping andmultiplexing according to embodiments of the present disclosure;

FIG. 21 illustrates an example capability to resist CFO according toembodiments of the present disclosure;

FIG. 22 illustrates an example PAPR according to embodiments of thepresent disclosure;

FIG. 23 illustrates an example RCM value according to embodiments of thepresent disclosure;

FIG. 24 illustrates another example capability to resist CFO accordingto embodiments of the present disclosure;

FIG. 25 illustrates yet another example capability to resist CFOaccording to embodiments of the present disclosure;

FIG. 26 illustrates yet another example capability to resist CFOaccording to embodiments of the present disclosure;

FIG. 27 illustrates yet another example capability to resist CFOaccording to embodiments of the present disclosure; and

FIG. 28 illustrates an example mapping pattern according to embodimentsof the present disclosure.

DETAILED DESCRIPTION

FIG. 1 through FIG. 28, discussed below, and the various embodimentsused to describe the principles of the present disclosure in this patentdocument are by way of illustration only and should not be construed inany way to limit the scope of the disclosure. Those skilled in the artwill understand that the principles of the present disclosure may beimplemented in any suitably arranged system or device.

The following documents and standards descriptions are herebyincorporated by reference into the present disclosure as if fully setforth herein: 3GPP TS 36.211 v13.2.0, “E-UTRA, Physical channels andmodulation;” 3GPP TS 36.212 v13.2.0, “E-UTRA, Multiplexing and Channelcoding;” 3GPP TS 36.213 v13.2.0, “E-UTRA, Physical Layer Procedures;”3GPP TS 36.321 v13.2.0, “E-UTRA, Medium Access Control (MAC) protocolspecification;” and 3GPP TS 36.331 v13.2.0, “E-UTRA, Radio ResourceControl (RRC) protocol specification.”

To meet the demand for wireless data traffic having increased sincedeployment of 4G communication systems, efforts have been made todevelop an improved 5G or pre-5G communication system. Therefore, the 5Gor pre-5G communication system is also called a “beyond 4G network” or a“post LTE system.”

The 5G communication system is considered to be implemented in higherfrequency (mmWave) bands, e.g., 60 GHz bands, so as to accomplish higherdata rates. To decrease propagation loss of the radio waves and increasethe transmission coverage, the beamforming, massive multiple-inputmultiple-output (MIMO), full dimensional MIMO (FD-MIMO), array antenna,an analog beam forming, large scale antenna techniques and the like arediscussed in 5G communication systems.

In addition, in 5G communication systems, development for system networkimprovement is under way based on advanced small cells, cloud radioaccess networks (RANs), ultra-dense networks, device-to-device (D2D)communication, wireless backhaul communication, moving network,cooperative communication, coordinated multi-points (CoMP) transmissionand reception, interference mitigation and cancellation and the like.

In the 5G system, hybrid frequency shift keying and quadrature amplitudemodulation (FQAM) and sliding window superposition coding (SWSC) as anadaptive modulation and coding (AMC) technique, and filter bank multicarrier (FBMC), non-orthogonal multiple access (NOMA), and sparse codemultiple access (SCMA) as an advanced access technology have beendeveloped.

FIGS. 1-4B below describe various embodiments implemented in wirelesscommunications systems and with the use of orthogonal frequency divisionmultiplexing (OFDM) or orthogonal frequency division multiple access(OFDMA) communication techniques. The descriptions of FIGS. 1-3 are notmeant to imply physical or architectural limitations to the manner inwhich different embodiments may be implemented. Different embodiments ofthe present disclosure may be implemented in any suitably-arrangedcommunications system.

FIG. 1 illustrates an example wireless network according to embodimentsof the present disclosure. The embodiment of the wireless network shownin FIG. 1 is for illustration only. Other embodiments of the wirelessnetwork 100 could be used without departing from the scope of thisdisclosure.

As shown in FIG. 1, the wireless network includes an eNB 101, an eNB102, and an eNB 103. The eNB 101 communicates with the eNB 102 and theeNB 103. The eNB 101 also communicates with at least one network 130,such as the Internet, a proprietary Internet Protocol (IP) network, orother data network.

The eNB 102 provides wireless broadband access to the network 130 for afirst plurality of user equipments (UEs) within a coverage area 120 ofthe eNB 102. The first plurality of UEs includes a UE 111, which may belocated in a small business (SB); a UE 112, which may be located in anenterprise (E); a UE 113, which may be located in a WiFi hotspot (HS); aUE 114, which may be located in a first residence (R); a UE 115, whichmay be located in a second residence (R); and a UE 116, which may be amobile device (M), such as a cell phone, a wireless laptop, a wirelessPDA, or the like. The eNB 103 provides wireless broadband access to thenetwork 130 for a second plurality of UEs within a coverage area 125 ofthe eNB 103. The second plurality of UEs includes the UE 115 and the UE116. In some embodiments, one or more of the eNBs 101-103 maycommunicate with each other and with the UEs 111-116 using 5G, LTE,LTE-A, WiMAX, WiFi, or other wireless communication techniques.

Depending on the network type, the term “base station” or “BS” can referto any component (or collection of components) configured to providewireless access to a network, such as transmit point (TP),transmit-receive point (TRP), an enhanced base station (eNodeB or eNB),a 5G base station (gNB), a macrocell, a femtocell, a WiFi access point(AP), or other wirelessly enabled devices. Base stations may providewireless access in accordance with one or more wireless communicationprotocols, e.g., 5G 3GPP new radio interface/access (NR), long termevolution (LTE), LTE advanced (LTE-A), high speed packet access (HSPA),Wi-Fi 802.11a/b/g/n/ac, etc. For the sake of convenience, the terms “BS”and “TRP” are used interchangeably in this patent document to refer tonetwork infrastructure components that provide wireless access to remoteterminals. Also, depending on the network type, the term “userequipment” or “UE” can refer to any component such as “mobile station,”“subscriber station,” “remote terminal,” “wireless terminal,” “receivepoint,” or “user device.” For the sake of convenience, the terms “userequipment” and “UE” are used in this patent document to refer to remotewireless equipment that wirelessly accesses a BS, whether the UE is amobile device (such as a mobile telephone or smartphone) or is normallyconsidered a stationary device (such as a desktop computer or vendingmachine).

Dotted lines show the approximate extents of the coverage areas 120 and125, which are shown as approximately circular for the purposes ofillustration and explanation only. It should be clearly understood thatthe coverage areas associated with eNBs, such as the coverage areas 120and 125, may have other shapes, including irregular shapes, dependingupon the configuration of the eNBs and variations in the radioenvironment associated with natural and man-made obstructions.

As described in more detail below, one or more of the UEs 111-116include circuitry, programming, or a combination thereof, for efficientCSI reporting on PUCCH in an advanced wireless communication system. Incertain embodiments, and one or more of the eNBs 101-103 includescircuitry, programming, or a combination thereof, for receivingefficient CSI reporting on PUCCH in an advanced wireless communicationsystem.

Although FIG. 1 illustrates one example of a wireless network, variouschanges may be made to FIG. 1. For example, the wireless network couldinclude any number of eNBs and any number of UEs in any suitablearrangement. Also, the eNB 101 could communicate directly with anynumber of UEs and provide those UEs with wireless broadband access tothe network 130. Similarly, each eNB 102-103 could communicate directlywith the network 130 and provide UEs with direct wireless broadbandaccess to the network 130. Further, the eNBs 101, 102, and/or 103 couldprovide access to other or additional external networks, such asexternal telephone networks or other types of data networks.

FIG. 2 illustrates an example eNB 102 according to embodiments of thepresent disclosure. The embodiment of the eNB 102 illustrated in FIG. 2is for illustration only, and the eNBs 101 and 103 of FIG. 1 could havethe same or similar configuration. However, eNBs come in a wide varietyof configurations, and FIG. 2 does not limit the scope of thisdisclosure to any particular implementation of an eNB.

As shown in FIG. 2, the eNB 102 includes multiple antennas 205 a-205 n,multiple RF transceivers 210 a-210 n, transmit (TX) processing circuitry215, and receive (RX) processing circuitry 220. The eNB 102 alsoincludes a controller/processor 225, a memory 230, and a backhaul ornetwork interface 235.

The RF transceivers 210 a-210 n receive, from the antennas 205 a-205 n,incoming RF signals, such as signals transmitted by UEs in the network100. The RF transceivers 210 a-210 n down-convert the incoming RFsignals to generate IF or baseband signals. The IF or baseband signalsare sent to the RX processing circuitry 220, which generates processedbaseband signals by filtering, decoding, and/or digitizing the basebandor IF signals. The RX processing circuitry 220 transmits the processedbaseband signals to the controller/processor 225 for further processing.

In some embodiments, the RF transceiver 210 a-201 n is capable oftransmitting the PSS and SSS over downlink channels.

The TX processing circuitry 215 receives analog or digital data (such asvoice data, web data, e-mail, or interactive video game data) from thecontroller/processor 225. The TX processing circuitry 215 encodes,multiplexes, and/or digitizes the outgoing baseband data to generateprocessed baseband or IF signals. The RF transceivers 210 a-210 nreceive the outgoing processed baseband or IF signals from the TXprocessing circuitry 215 and up-converts the baseband or IF signals toRF signals that are transmitted via the antennas 205 a-205 n.

The controller/processor 225 can include one or more processors or otherprocessing devices that control the overall operation of the eNB 102.For example, the controller/processor 225 could control the reception offorward channel signals and the transmission of reverse channel signalsby the RF transceivers 210 a-210 n, the RX processing circuitry 220, andthe TX processing circuitry 215 in accordance with well-knownprinciples. The controller/processor 225 could support additionalfunctions as well, such as more advanced wireless communicationfunctions. For instance, the controller/processor 225 could support beamforming or directional routing operations in which outgoing signals frommultiple antennas 205 a-205 n are weighted differently to effectivelysteer the outgoing signals in a desired direction. Any of a wide varietyof other functions could be supported in the eNB 102 by thecontroller/processor 225.

The controller/processor 225 is also capable of executing programs andother processes resident in the memory 230, such as an OS. Thecontroller/processor 225 can move data into or out of the memory 230 asrequired by an executing process.

The controller/processor 225 is also coupled to the backhaul or networkinterface 235. The backhaul or network interface 235 allows the eNB 102to communicate with other devices or systems over a backhaul connectionor over a network. The interface 235 could support communications overany suitable wired or wireless connection(s). For example, when the eNB102 is implemented as part of a cellular communication system (such asone supporting 5G, LTE, or LTE-A), the interface 235 could allow the eNB102 to communicate with other eNBs over a wired or wireless backhaulconnection. When the eNB 102 is implemented as an access point, theinterface 235 could allow the eNB 102 to communicate over a wired orwireless local area network or over a wired or wireless connection to alarger network (such as the Internet). The interface 235 includes anysuitable structure supporting communications over a wired or wirelessconnection, such as an Ethernet or RF transceiver.

In some embodiments, the controller/processor 225 is capable ofgenerating a primary synchronization signal (PSS) including one ofmultiple PSS sequences that is generated based on a binary phase shiftkeying (BPSK) modulated length-127 M-sequence in a frequency domain,wherein the PSS includes part of cell identification (ID) information.

In some embodiments, the controller/processor 225 is capable ofgenerating a secondary synchronization signal (SSS) including one ofmultiple SSS sequences that is generated based on multiple BPSKmodulated length-127 M-sequences in the frequency domain, wherein theSSS includes the cell identification (ID) information.

In some embodiments, the controller/processor 225 is capable ofdetermining a number of PSS sequences corresponding to a number of cellID hypotheses carried by PSS, respectively and a number of SSS sequencescorresponding to the number of cell ID hypotheses carried by the PSS andSSS, respectively.

In some embodiments, the controller/processor 225 is capable ofdetermining a polynomial for an M-sequence generating the PSS sequenceand a cyclic shift for the M-sequence based on the cell ID informationcarried by PSS, and generating the PSS sequence by performing the cyclicshift to the M-sequence for a cell ID.

In some embodiments, the controller/processor 225 is capable ofdetermining a polynomial for a first M-sequence generating the SSSsequence, a first cyclic shift for the first M-sequence based on thecell ID information carried by PSS and SSS, the polynomial for a secondM-sequence generating the SSS sequence, a second cyclic shift for thesecond M-sequence based on the cell ID information carried by PSS andSSS, and generating the SSS sequence by performing a product of thefirst and second M-sequences, wherein each of the first and secondM-sequences is generated by the first and second cyclic shifts,respectively, for the cell ID.

In such embodiments, the polynomial for the M-sequence is given byx⁷+x⁴+1 and a corresponding recursive construction scheme is given byd_(M)(i+7)=[d_(M)(i+4)+d_(M)(i)]mod 2, 0≤i≤119, the polynomial for thefirst M-sequence is given by x⁷+x⁴+1 and a corresponding recursiveconstruction scheme is given by d_(M)(i+7)=[d_(M)(i+4)+d_(M)(i)]mod 2,0≤i≤119, and the polynomial for the second M-sequence is given by x⁷+x+1and a corresponding recursive construction scheme is given byd_(M)(i+7)=[d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤119.

The memory 230 is coupled to the controller/processor 225. Part of thememory 230 could include a RAM, and another part of the memory 230 couldinclude a Flash memory or other ROM.

Although FIG. 2 illustrates one example of eNB 102, various changes maybe made to FIG. 2. For example, the eNB 102 could include any number ofeach component shown in FIG. 2. As a particular example, an access pointcould include a number of interfaces 235, and the controller/processor225 could support routing functions to route data between differentnetwork addresses. As another particular example, while shown asincluding a single instance of TX processing circuitry 215 and a singleinstance of RX processing circuitry 220, the eNB 102 could includemultiple instances of each (such as one per RF transceiver). Also,various components in FIG. 2 could be combined, further subdivided, oromitted and additional components could be added according to particularneeds.

FIG. 3 illustrates an example UE 116 according to embodiments of thepresent disclosure. The embodiment of the UE 116 illustrated in FIG. 3is for illustration only, and the UEs 111-115 of FIG. 1 could have thesame or similar configuration. However, UEs come in a wide variety ofconfigurations, and FIG. 3 does not limit the scope of this disclosureto any particular implementation of a UE.

As shown in FIG. 3, the UE 116 includes an antenna 305, a radiofrequency (RF) transceiver 310, TX processing circuitry 315, amicrophone 320, and receive (RX) processing circuitry 325. The UE 116also includes a speaker 330, a processor 340, an input/output (I/O)interface (IF) 345, a touchscreen 350, a display 355, and a memory 360.The memory 360 includes an operating system (OS) 361 and one or moreapplications 362.

The RF transceiver 310 receives, from the antenna 305, an incoming RFsignal transmitted by an eNB of the network 100. The RF transceiver 310down-converts the incoming RF signal to generate an intermediatefrequency (IF) or baseband signal. The IF or baseband signal is sent tothe RX processing circuitry 325, which generates a processed basebandsignal by filtering, decoding, and/or digitizing the baseband or IFsignal. The RX processing circuitry 325 transmits the processed basebandsignal to the speaker 330 (such as for voice data) or to the processor340 for further processing (such as for web browsing data).

In some embodiments, the RF transceiver 310 is capable of receiving aprimary synchronization signal (PSS) and a secondary synchronizationsignal (SSS) over downlink channels.

The TX processing circuitry 315 receives analog or digital voice datafrom the microphone 320 or other outgoing baseband data (such as webdata, e-mail, or interactive video game data) from the processor 340.The TX processing circuitry 315 encodes, multiplexes, and/or digitizesthe outgoing baseband data to generate a processed baseband or IFsignal. The RF transceiver 310 receives the outgoing processed basebandor IF signal from the TX processing circuitry 315 and up-converts thebaseband or IF signal to an RF signal that is transmitted via theantenna 305.

The processor 340 can include one or more processors or other processingdevices and execute the OS 361 stored in the memory 360 in order tocontrol the overall operation of the UE 116. For example, the processor340 could control the reception of forward channel signals and thetransmission of reverse channel signals by the RF transceiver 310, theRX processing circuitry 325, and the TX processing circuitry 315 inaccordance with well-known principles. In some embodiments, theprocessor 340 includes at least one microprocessor or microcontroller.

The processor 340 is also capable of executing other processes andprograms resident in the memory 360, such as processes for CSI reportingon PUCCH. The processor 340 can move data into or out of the memory 360as required by an executing process. In some embodiments, the processor340 is configured to execute the applications 362 based on the OS 361 orin response to signals received from eNBs or an operator. The processor340 is also coupled to the I/O interface 345, which provides the UE 116with the ability to connect to other devices, such as laptop computersand handheld computers. The I/O interface 345 is the communication pathbetween these accessories and the processor 340.

The processor 340 is also coupled to the touchscreen 350 and the display355. The operator of the UE 116 can use the touchscreen 350 to enterdata into the UE 116. The display 355 may be a liquid crystal display,light emitting diode display, or other display capable of rendering textand/or at least limited graphics, such as from web sites.

In some embodiments, the processor 340 is capable of determining the PSSincluding one of multiple PSS sequences that is generated based on abinary phase shift keying (BPSK) modulated length-127 M-sequence in afrequency domain, wherein the PSS includes part of cell identification(ID) information and the SSS including one of multiple SSS sequencesthat is generated based on multiple BPSK modulated length-127M-sequences in the frequency domain, wherein the SSS includes the cellidentification (ID) information.

In some embodiments, the processor 340 is capable of determining anumber of PSS sequences corresponding to a number of cell ID hypothesescarried by PSS, respectively; and a number of SSS sequencescorresponding to the number of cell ID hypotheses carried by the PSS andSSS, respectively.

In some embodiments, the processor 340 is capable of determining apolynomial for an M-sequence generating the PSS sequence, a cyclic shiftfor the M-sequence based on the cell ID information carried by PSS, andgenerating the PSS sequence by performing the cyclic shift to theM-sequence for a cell ID.

In some embodiments, the processor 340 is capable of determining apolynomial for a first M-sequence generating the SSS sequence, a firstcyclic shift for the first M-sequence based on the cell ID informationcarried by PSS and SSS, the polynomial for a second M-sequencegenerating the SSS sequence, a second cyclic shift for the secondM-sequence based on the cell ID information carried by PSS and SSS, andgenerating the SSS sequence by performing a product of the first andsecond M-sequences, wherein each of the first and second M-sequences isgenerated by the first and second cyclic shifts, respectively, for thecell ID.

In such embodiments, the polynomial for the M-sequence is given byx⁷+x⁴+1 and a corresponding recursive construction scheme is given byd_(M)(i+7)=[d_(M)(i+4)+d_(M)(i)]mod 2, 0≤i≤119, the polynomial for thefirst M-sequence is given by x⁷+x⁴+1 and a corresponding recursiveconstruction scheme is given by d_(M)(i+7)=[d_(M)(i+4)+d_(M)(i)]mod 2,0≤i≤119, and the polynomial for the second M-sequence is given by x⁷+x+1and a corresponding recursive construction scheme is given byd_(M)(i+7)=[d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤119.

The memory 360 is coupled to the processor 340. Part of the memory 360could include a random access memory (RAM), and another part of thememory 360 could include a Flash memory or other read-only memory (ROM).

Although FIG. 3 illustrates one example of UE 116, various changes maybe made to FIG. 3. For example, various components in FIG. 3 could becombined, further subdivided, or omitted and additional components couldbe added according to particular needs. As a particular example, theprocessor 340 could be divided into multiple processors, such as one ormore central processing units (CPUs) and one or more graphics processingunits (GPUs). Also, while FIG. 3 illustrates the UE 116 configured as amobile telephone or smartphone, UEs could be configured to operate asother types of mobile or stationary devices.

FIG. 4A is a high-level diagram of transmit path circuitry. For example,the transmit path circuitry may be used for an orthogonal frequencydivision multiple access (OFDMA) communication. FIG. 4B is a high-leveldiagram of receive path circuitry. For example, the receive pathcircuitry may be used for an orthogonal frequency division multipleaccess (OFDMA) communication. In FIGS. 4A and 4B, for downlinkcommunication, the transmit path circuitry may be implemented in a basestation (eNB) 102 or a relay station, and the receive path circuitry maybe implemented in a user equipment (e.g. user equipment 116 of FIG. 1).In other examples, for uplink communication, the receive path circuitry450 may be implemented in a base station (e.g. eNB 102 of FIG. 1) or arelay station, and the transmit path circuitry may be implemented in auser equipment (e.g. user equipment 116 of FIG. 1).

Transmit path circuitry comprises channel coding and modulation block405, serial-to-parallel (S-to-P) block 410, Size N Inverse Fast FourierTransform (IFFT) block 415, parallel-to-serial (P-to-S) block 420, addcyclic prefix block 425, and up-converter (UC) 430. Receive pathcircuitry 450 comprises down-converter (DC) 455, remove cyclic prefixblock 460, serial-to-parallel (S-to-P) block 465, Size N Fast FourierTransform (FFT) block 470, parallel-to-serial (P-to-S) block 475, andchannel decoding and demodulation block 480.

At least some of the components in FIGS. 4A 400 and 4B 450 may beimplemented in software, while other components may be implemented byconfigurable hardware or a mixture of software and configurablehardware. In particular, it is noted that the FFT blocks and the IFFTblocks described in this disclosure document may be implemented asconfigurable software algorithms, where the value of Size N may bemodified according to the implementation.

Furthermore, although this disclosure is directed to an embodiment thatimplements the Fast Fourier Transform and the Inverse Fast FourierTransform, this is by way of illustration only and may not be construedto limit the scope of the disclosure. It may be appreciated that in analternate embodiment of the present disclosure, the Fast FourierTransform functions and the Inverse Fast Fourier Transform functions mayeasily be replaced by discrete Fourier transform (DFT) functions andinverse discrete Fourier transform (IDFT) functions, respectively. Itmay be appreciated that for DFT and IDFT functions, the value of the Nvariable may be any integer number (i.e., 1, 4, 3, 4, etc.), while forFFT and IFFT functions, the value of the N variable may be any integernumber that is a power of two (i.e., 1, 2, 4, 8, 16, etc.).

In transmit path circuitry 400, channel coding and modulation block 405receives a set of information bits, applies coding (e.g., LDPC coding)and modulates (e.g., quadrature phase shift keying (QPSK) or quadratureamplitude modulation (QAM)) the input bits to produce a sequence offrequency-domain modulation symbols. Serial-to-parallel block 410converts (i.e., de-multiplexes) the serial modulated symbols to paralleldata to produce N parallel symbol streams where N is the IFFT/FFT sizeused in BS 102 and UE 116. Size N IFFT block 415 then performs an IFFToperation on the N parallel symbol streams to produce time-domain outputsignals. Parallel-to-serial block 420 converts (i.e., multiplexes) theparallel time-domain output symbols from Size N IFFT block 415 toproduce a serial time-domain signal. Add cyclic prefix block 425 theninserts a cyclic prefix to the time-domain signal. Finally, up-converter430 modulates (i.e., up-converts) the output of add cyclic prefix block425 to RF frequency for transmission via a wireless channel. The signalmay also be filtered at baseband before conversion to RF frequency.

The transmitted RF signal arrives at UE 116 after passing through thewireless channel, and reverse operations to those at eNB 102 areperformed. Down-converter 455 down-converts the received signal tobaseband frequency, and remove cyclic prefix block 460 removes thecyclic prefix to produce the serial time-domain baseband signal.Serial-to-parallel block 465 converts the time-domain baseband signal toparallel time-domain signals. Size N FFT block 470 then performs an FFTalgorithm to produce N parallel frequency-domain signals.Parallel-to-serial block 475 converts the parallel frequency-domainsignals to a sequence of modulated data symbols. Channel decoding anddemodulation block 480 demodulates and then decodes the modulatedsymbols to recover the original input data stream.

Each of eNBs 101-103 may implement a transmit path that is analogous totransmitting in the downlink to user equipment 111-116 and may implementa receive path that is analogous to receiving in the uplink from userequipment 111-116. Similarly, each one of user equipment 111-116 mayimplement a transmit path corresponding to the architecture fortransmitting in the uplink to eNBs 101-103 and may implement a receivepath corresponding to the architecture for receiving in the downlinkfrom eNBs 101-103.

5G communication system use cases have been identified and described.Those use cases can be roughly categorized into three different groups.In one example, enhanced mobile broadband (eMBB) is determined to dowith high bits/sec requirement, with less stringent latency andreliability requirements. In another example, ultra reliable and lowlatency (URLL) is determined with less stringent bits/sec requirement.In yet another example, massive machine type communication (mMTC) isdetermined that a number of devices can be as many as 100,000 to 1million per km2, but the reliability/throughput/latency requirementcould be less stringent. This scenario may also involve power efficiencyrequirement as well, in that the battery consumption should be minimizedas possible.

A communication system includes a Downlink (DL) that conveys signalsfrom transmission points such as Base Stations (BSs) or NodeBs to UserEquipments (UEs) and an Uplink (UL) that conveys signals from UEs toreception points such as NodeBs. A UE, also commonly referred to as aterminal or a mobile station, may be fixed or mobile and may be acellular phone, a personal computer device, or an automated device. AneNodeB, which is generally a fixed station, may also be referred to asan access point or other equivalent terminology. For LTE systems, aNodeB is often referred as an eNodeB.

In a communication system, such as LTE system, DL signals can includedata signals conveying information content, control signals conveying DLcontrol information (DCI), and reference signals (RS) that are alsoknown as pilot signals. An eNodeB transmits data information through aphysical DL shared channel (PDSCH). An eNodeB transmits DCI through aphysical DL control channel (PDCCH) or an Enhanced PDCCH (EPDCCH).

An eNodeB transmits acknowledgement information in response to datatransport block (TB) transmission from a UE in a physical hybrid ARQindicator channel (PHICH). An eNodeB transmits one or more of multipletypes of RS including a UE-common RS (CRS), a channel state informationRS (CSI-RS), or a demodulation RS (DMRS). A CRS is transmitted over a DLsystem bandwidth (BW) and can be used by UEs to obtain a channelestimate to demodulate data or control information or to performmeasurements. To reduce CRS overhead, an eNodeB may transmit a CSI-RSwith a smaller density in the time and/or frequency domain than a CRS.DMRS can be transmitted only in the BW of a respective PDSCH or EPDCCHand a UE can use the DMRS to demodulate data or control information in aPDSCH or an EPDCCH, respectively. A transmission time interval for DLchannels is referred to as a subframe and can have, for example,duration of 1 millisecond.

DL signals also include transmission of a logical channel that carriessystem control information. A BCCH is mapped to either a transportchannel referred to as a broadcast channel (BCH) when it conveys amaster information block (MIB) or to a DL shared channel (DL-SCH) whenit conveys a System Information Block (SIB). Most system information isincluded in different SIBs that are transmitted using DL-SCH. A presenceof system information on a DL-SCH in a subframe can be indicated by atransmission of a corresponding PDCCH conveying a codeword with a cyclicredundancy check (CRC) scrambled with special system information RNTI(SI-RNTI). Alternatively, scheduling information for a SIB transmissioncan be provided in an earlier SIB and scheduling information for thefirst SIB (SIB-1) can be provided by the MIB.

DL resource allocation is performed in a unit of subframe and a group ofphysical resource blocks (PRBs). A transmission BW includes frequencyresource units referred to as resource blocks (RBs). Each RB includesN_(sc) ^(RB) sub-carriers, or resource elements (REs), such as 12 REs. Aunit of one RB over one subframe is referred to as a PRB. A UE can beallocated M_(PDSCH) RBs for a total of M_(sc) ^(PDSCH)=M_(PDSCH)·N_(sc)^(RB) REs for the PDSCH transmission BW.

UL signals can include data signals conveying data information, controlsignals conveying UL control information (UCI), and UL RS. UL RSincludes DMRS and Sounding RS (SRS). A UE transmits DMRS only in a BW ofa respective PUSCH or PUCCH. An eNodeB can use a DMRS to demodulate datasignals or UCI signals. A UE transmits SRS to provide an eNodeB with anUL CSI. A UE transmits data information or UCI through a respectivephysical UL shared channel (PUSCH) or a Physical UL control channel(PUCCH). If a UE needs to transmit data information and UCI in a same ULsubframe, it may multiplex both in a PUSCH. UCI includes HybridAutomatic Repeat request acknowledgement (HARQ-ACK) information,indicating correct (ACK) or incorrect (NACK) detection for a data TB ina PDSCH or absence of a PDCCH detection (DTX), scheduling request (SR)indicating whether a UE has data in the UE's buffer, rank indicator(RI), and channel state information (CSI) enabling an eNodeB to performlink adaptation for PDSCH transmissions to a UE. HARQ-ACK information isalso transmitted by a UE in response to a detection of a PDCCH/EPDCCHindicating a release of semi-persistently scheduled PDSCH.

An UL subframe includes two slots. Each slot includes N_(symb) ^(UL)symbols for transmitting data information, UCI, DMRS, or SRS. Afrequency resource unit of an UL system BW is a RB. A UE is allocatedN_(RB) RBs for a total of N_(RB)·N_(sc) ^(RB) REs for a transmission BW.For a PUCCH, N_(RB)=1. A last subframe symbol can be used to multiplexSRS transmissions from one or more UEs. A number of subframe symbolsthat are available for data/UCI/DMRS transmission isN_(symb)=2·(N_(symb) ^(UL)−1)−N_(SRS), where N_(SRS)=1 if a lastsubframe symbol is used to transmit SRS and N_(SRS)=0 otherwise.

FIG. 5 illustrates a transmitter block diagram 500 for a PDSCH in asubframe according to embodiments of the present disclosure. Theembodiment of the transmitter block diagram 500 illustrated in FIG. 5 isfor illustration only. FIG. 5 does not limit the scope of thisdisclosure to any particular implementation of the transmitter blockdiagram 500.

As shown in FIG. 5, information bits 510 are encoded by encoder 520,such as a turbo encoder, and modulated by modulator 530, for exampleusing quadrature phase shift keying (QPSK) modulation. A serial toparallel (S/P) converter 540 generates M modulation symbols that aresubsequently provided to a mapper 550 to be mapped to REs selected by atransmission BW selection unit 555 for an assigned PDSCH transmissionBW, unit 560 applies an Inverse fast Fourier transform (IFFT), theoutput is then serialized by a parallel to serial (P/S) converter 570 tocreate a time domain signal, filtering is applied by filter 580, and asignal transmitted 590. Additional functionalities, such as datascrambling, cyclic prefix insertion, time windowing, interleaving, andothers are well known in the art and are not shown for brevity.

FIG. 6 illustrates a receiver block diagram 600 for a PDSCH in asubframe according to embodiments of the present disclosure. Theembodiment of the diagram 600 illustrated in FIG. 6 is for illustrationonly. FIG. 6 does not limit the scope of this disclosure to anyparticular implementation of the diagram 600.

As shown in FIG. 6, a received signal 610 is filtered by filter 620, REs630 for an assigned reception BW are selected by BW selector 635, unit640 applies a fast Fourier transform (FFT), and an output is serializedby a parallel-to-serial converter 650. Subsequently, a demodulator 660coherently demodulates data symbols by applying a channel estimateobtained from a DMRS or a CRS (not shown), and a decoder 670, such as aturbo decoder, decodes the demodulated data to provide an estimate ofthe information data bits 680. Additional functionalities such astime-windowing, cyclic prefix removal, de-scrambling, channelestimation, and de-interleaving are not shown for brevity.

FIG. 7 illustrates a transmitter block diagram 700 for a PUSCH in asubframe according to embodiments of the present disclosure. Theembodiment of the block diagram 700 illustrated in FIG. 7 is forillustration only. FIG. 7 does not limit the scope of this disclosure toany particular implementation of the block diagram 700.

As shown in FIG. 7, information data bits 710 are encoded by encoder720, such as a turbo encoder, and modulated by modulator 730. A discreteFourier transform (DFT) unit 740 applies a DFT on the modulated databits, REs 750 corresponding to an assigned PUSCH transmission BW areselected by transmission BW selection unit 755, unit 760 applies an IFFTand, after a cyclic prefix insertion (not shown), filtering is appliedby filter 770 and a signal transmitted 780.

FIG. 8 illustrates a receiver block diagram 800 for a PUSCH in asubframe according to embodiments of the present disclosure. Theembodiment of the block diagram 800 illustrated in FIG. 8 is forillustration only. FIG. 8 does not limit the scope of this disclosure toany particular implementation of the block diagram 800.

As shown in FIG. 8, a received signal 810 is filtered by filter 820.Subsequently, after a cyclic prefix is removed (not shown), unit 830applies a FFT, REs 840 corresponding to an assigned PUSCH reception BWare selected by a reception BW selector 845, unit 850 applies an inverseDFT (IDFT), a demodulator 860 coherently demodulates data symbols byapplying a channel estimate obtained from a DMRS (not shown), a decoder870, such as a turbo decoder, decodes the demodulated data to provide anestimate of the information data bits 880.

In next generation cellular systems, various use cases are envisionedbeyond the capabilities of LTE system. Termed 5G or the fifth generationcellular system, a system capable of operating at sub-6 GHz and above-6GHz (for example, in mmWave regime) becomes one of the requirements. In3GPP TR 22.891, 74 5G use cases has been identified and described; thoseuse cases can be roughly categorized into three different groups. Afirst group is termed ‘enhanced mobile broadband’ (eMBB), targeted tohigh data rate services with less stringent latency and reliabilityrequirements. A second group is termed “ultra-reliable and low latency(URLL)” targeted for applications with less stringent data raterequirements, but less tolerant to latency. A third group is termed“massive MTC (mMTC)” targeted for large number of low-power deviceconnections such as 1 million per km² with less stringent thereliability, data rate, and latency requirements.

In order for the 5G network to support such diverse services withdifferent quality of services (QoS), one method has been identified inLTE specification, called network slicing. To utilize PHY resourcesefficiently and multiplex various slices (with different resourceallocation schemes, numerologies, and scheduling strategies) in DL-SCH,a flexible and self-contained frame or subframe design is utilized.

FIG. 9 illustrates an example multiplexing of two slices 900 accordingto embodiments of the present disclosure. The embodiment of themultiplexing of two slices 900 illustrated in FIG. 9 is for illustrationonly. FIG. 9 does not limit the scope of this disclosure to anyparticular implementation of the multiplexing of two slices 900.

Two exemplary instances of multiplexing two slices within a commonsubframe or frame are depicted in FIG. 9. In these exemplaryembodiments, a slice can be composed of one or two transmissioninstances where one transmission instance includes a control (CTRL)component (e.g., 920 a, 960 a, 960 b, 920 b, or 960 c) and a datacomponent (e.g., 930 a, 970 a, 970 b, 930 b, or 970 c). In embodiment910, the two slices are multiplexed in frequency domain whereas inembodiment 950, the two slices are multiplexed in time domain. These twoslices can be transmitted with different sets of numerology.

LTE specification supports up to 32 CSI-RS antenna ports which enable aneNB to be equipped with a large number of antenna elements (such as 64or 128). In this case, a plurality of antenna elements is mapped ontoone CSI-RS port. For next generation cellular systems such as 5G, themaximum number of CSI-RS ports can either remain the same or increase.

FIG. 10 illustrates an example antenna blocks 1000 according toembodiments of the present disclosure. The embodiment of the antennablocks 1000 illustrated in FIG. 10 is for illustration only. FIG. 10does not limit the scope of this disclosure to any particularimplementation of the antenna blocks 1000.

For mmWave bands, although the number of antenna elements can be largerfor a given form factor, the number of CSI-RS ports—which can correspondto the number of digitally precoded ports—tends to be limited due tohardware constraints (such as the feasibility to install a large numberof ADCs/DACs at mmWave frequencies) as illustrated in FIG. 10. In thiscase, one CSI-RS port is mapped onto a large number of antenna elementswhich can be controlled by a bank of analog phase shifters. One CSI-RSport can then correspond to one sub-array which produces a narrow analogbeam through analog beamforming. This analog beam can be configured tosweep across a wider range of angles by varying the phase shifter bankacross symbols or subframes. The number of sub-arrays (equal to thenumber of RF chains) is the same as the number of CSI-RS portsN_(CSI-PORT). A digital beamforming unit performs a linear combinationacross N_(CSI-PORT) analog beams to further increase precoding gain.While analog beams are wideband (hence not frequency-selective), digitalprecoding can be varied across frequency sub-bands or resource blocks.

In a 3GPP LTE communication system, network access and radio resourcemanagement (RRM) are enabled by physical layer synchronization signalsand higher (MAC) layer procedures. In particular, a UE attempts todetect the presence of synchronization signals along with at least onecell ID for initial access. Once the UE is in the network and associatedwith a serving cell, the UE monitors several neighboring cells byattempting to detect their synchronization signals and/or measuring theassociated cell-specific RSs (for instance, by measuring their RSRPs).For next generation cellular systems such as 3GPP NR (new radio accessor interface), efficient and unified radio resource acquisition ortracking mechanism which works for various use cases (such as eMBB,URLLC, mMTC, each corresponding to a different coverage requirement) andfrequency bands (with different propagation losses) is desirable. Mostlikely designed with a different network and radio resource paradigm,seamless and low-latency RRM is also desirable. Such goals pose at leastthe following problems in designing an access, radio resource, andmobility management framework.

First, since NR is likely to support even more diversified networktopology, the notion of cell can be redefined or replaced with anotherradio resource entity. As an example, for synchronous networks, one cellcan be associated with a plurality of TRPs (transmit-receive points)similar to a COMP (coordinated multipoint transmission) scenario in LTEspecification. In this case, seamless mobility is a desirable feature.

Second, when large antenna arrays and beamforming are utilized, definingradio resource in terms of beams (although possibly termed differently)can be a natural approach. Given that numerous beamforming architecturescan be utilized, an access, radio resource, and mobility managementframework which accommodates various beamforming architectures (or,instead, agnostic to beamforming architecture) is desirable.

FIG. 11 illustrates an example UE mobility scenario 1100 according toembodiments of the present disclosure. The embodiment of the UE mobilityscenario 1100 illustrated in FIG. 11 is for illustration only. FIG. 11does not limit the scope of this disclosure to any particularimplementation of the UE mobility scenario 1100.

For instance, the framework may be applicable for or agnostic to whetherone beam is formed for one CSI-RS port (for instance, where a pluralityof analog ports are connected to one digital port, and a plurality ofwidely separated digital ports are utilized) or one beam is formed by aplurality of CSI-RS ports. In addition, the framework may be applicablewhether beam sweeping (as illustrated in FIG. 11) is used or not.

Third, different frequency bands and use cases impose different coveragelimitations. For example, mmWave bands impose large propagation losses.Therefore, some form of coverage enhancement scheme is needed. Severalcandidates include beam sweeping (as shown in FIG. 10), repetition,diversity, and/or multi-TRP transmission. For mMTC where transmissionbandwidth is small, time-domain repetition is needed to ensuresufficient coverage.

A UE-centric access which utilizes two levels of radio resource entityis described in FIG. 11. These two levels can be termed as “cell” and“beam”. These two terms are exemplary and used for illustrativepurposes. Other terms such as radio resource (RR) 1 and 2 can also beused. Additionally, the term “beam” as a radio resource unit is to bedifferentiated with, for instance, an analog beam used for beam sweepingin FIG. 10.

As shown in FIG. 11, the first RR level (termed “cell”) applies when aUE enters a network and therefore is engaged in an initial accessprocedure. In 1110, a UE 1111 is connected to cell 1112 after performingan initial access procedure which includes detecting the presence ofsynchronization signals. Synchronization signals can be used for coarsetiming and frequency acquisitions as well as detecting the cellidentification (cell ID) associated with the serving cell. In this firstlevel, the UE observes cell boundaries as different cells can beassociated with different cell IDs. In FIG. 11, one cell is associatedwith one TRP (in general, one cell can be associated with a plurality ofTRPs). Since cell ID is a MAC layer entity, initial access involves notonly physical layer procedure(s) (such as cell search viasynchronization signal acquisition) but also MAC layer procedure(s).

The second RR level (termed “beam”) applies when a UE is alreadyconnected to a cell and hence in the network. In this second level, a UE1111 can move within the network without observing cell boundaries asillustrated in embodiment 1150. That is, UE mobility is handled on beamlevel rather than cell level, where one cell can be associated with Nbeams (N can be 1 or >1). Unlike cell, however, beam is a physical layerentity. Therefore, UE mobility management is handled solely on physicallayer. An example of UE mobility scenario based on the second level RRis given in embodiment 1150 of FIG. 11.

After the UE 1111 is associated with the serving cell 1112, the UE 1111is further associated with beam 1151. This is achieved by acquiring abeam or radio resource (RR) acquisition signal from which the UE canacquire a beam identity or identification. An example of beam or RRacquisition signal is a measurement reference signal (RS). Uponacquiring a beam (or RR) acquisition signal, the UE 1111 can report astatus to the network or an associated TRP. Examples of such reportinclude a measured beam power (or measurement RS power) or a set of atleast one recommended “beam identity (ID)” or “RR-ID”. Based on thisreport, the network or the associated TRP can assign a beam (as a radioresource) to the UE 1111 for data and control transmission. When the UE1111 moves to another cell, the boundary between the previous and thenext cells is neither observed nor visible to the UE 1111. Instead ofcell handover, the UE 1111 switches from beam 1151 to beam 1152. Such aseamless mobility is facilitated by the report from UE 711 to thenetwork or associated TRP—especially when the UE 1111 reports a set ofM>1 preferred beam identities by acquiring and measuring M beam (or RR)acquisition signals.

FIG. 12 illustrates an example beam sweeping operation 1200 according toembodiments of the present disclosure. The embodiment of the beamsweeping operation 1200 illustrated in FIG. 12 is for illustration only.FIG. 12 does not limit the scope of this disclosure to any particularimplementation of the beam sweeping operation 1200.

As shown in FIG. 12, the aforementioned initial access procedure 1210and the aforementioned mobility or radio resource management 1220 fromthe perspective of a UE are described. The initial access procedure 1210includes cell ID acquisition from DL synchronization signal(s) 1211 aswell as retrieval of broadcast information (along with systeminformation required by the UE to establish DL and UL connections)followed by UL synchronization (which can include random accessprocedure) 1212. Once the UE completes 1211 and 1212, the UE isconnected to the network and associated with a cell. Following thecompletion of initial access procedure, the UE, possibly mobile, is inan RRM state described in 1220. This state includes, first, anacquisition stage 1221 where the UE can periodically (repeatedly)attempt to acquire a “beam” or RR ID from a “beam” or RR acquisitionsignal (such as a measurement RS).

The UE can be configured with a list of beam/RR IDs to monitor. Thislist of “beam”/RR IDs can be updated or reconfigured by the TRP/network.This configuration can be signaled via higher-layer (such as RRC)signaling or a dedicated L1 or L2 control channel. Based on this list,the UE can monitor and measure a signal associated with each of thesebeam/RR IDs. This signal can correspond to a measurement RS resourcesuch as that analogous to CSI-RS resource in LTE system. In this case,the UE can be configured with a set of K>1 CSI-RS resources to monitor.Several options are possible for measurement report 1222. First, the UEcan measure each of the K CSI-RS resources, calculate a corresponding RSpower (similar to RSRP or RSRQ in LTE system), and report it to the TRP(or network). Second, the UE can measure each of the K CSI-RS resources,calculate an associated CSI (which can include CQI and potentially otherCSI parameters such as RI and PMI), and report it to the TRP (ornetwork). Based on the report from the UE, the UE is assigned M≥1“beams” or RRs either via a higher-layer (RRC) signaling or an L1/L2control signaling 1223. Therefore the UE is connected to these M“beams”/RRs.

For certain scenarios such as asynchronous networks, the UE can fallback to cell ID based or cell-level mobility management similar to 3GPPLTE system. Therefore, only one of the two levels of radio resourceentity (cell) is applicable. When a two-level (“cell” and “beam”) radioresource entity or management is utilized, synchronization signal(s) canbe designed primarily for initial access into the network. For mmWavesystems where analog beam sweeping (as shown in FIG. 12) or repetitionmay be used for enhancing the coverage of common signals (such assynchronization signal(s) and broadcast channel), synchronizationsignals can be repeated across time (such as across OFDM symbols orslots or subframes). This repetition factor, however, is not necessarilycorrelated to the number of supported “beams” (defined as radio resourceunits, to be differentiated with the analog beams used in beam sweeping)per cell or per TRP. Therefore, beam identification (ID) is not acquiredor detected from synchronization signal(s). Instead, beam ID is carriedby a beam (RR) acquisition signal such as measurement RS. Likewise, beam(RR) acquisition signal does not carry cell ID (hence, cell ID is notdetected from beam or RR acquisition signal).

Therefore, considering the above new challenges in initial accessprocedure and RRM for the new radio access technology (NR), there is aneed for designing synchronization signals (along with their associatedUE procedures) and primary broadcast channel which carries broadcastinformation (e.g., master information block or MIB).

In the present disclosure, numerology refers to a set of signalparameters which can include subframe duration, sub-carrier spacing,cyclic prefix length, transmission bandwidth, or any combination ofthese signal parameters.

For LTE system, primary and secondary synchronization signals (PSS andSSS, respectively) are used for coarse timing and frequencysynchronization and cell ID acquisition. Since PSS/SSS is transmittedtwice per 10 ms radio frame and time-domain enumeration is introduced interms of system frame number (SFN, included in the MIB), frame timing isdetected from PSS/SSS to avoid the need for increasing the detectionburden from PBCH. In addition, cyclic prefix (CP) length and, ifunknown, duplexing scheme can be detected from PSS/SSS. The PSS isconstructed from a frequency-domain ZC sequence of length 63, with themiddle element truncated to avoid using the d.c. subcarrier.

Three roots are selected for PSS to represent the three physical layeridentities within each group of cells. The SSS sequences are based onthe maximum length sequences (also known as M-sequences). Each SSSsequence is constructed by interleaving two length-31 BPSK modulatedsequences in frequency domain, where the two source sequences beforemodulation are different cyclic shifts of the same M-sequence. Thecyclic shift indices are constructed from the physical cell ID group.Since PSS/SSS detection can be faulty, for example, due tonon-idealities in the auto- and cross-correlation properties of PSS/SSSand lack of CRC protection, cell ID hypotheses detected from PSS/SSS mayoccasionally be confirmed via PBCH detection. PBCH is primarily used tosignal the master block information (MIB) which includes DL and ULsystem bandwidth information (3 bits), PHICH information (3 bits), andSFN (8 bits).

Adding 10 reserved bits (for other uses such as MTC), the MIB payloadamounts to 24 bits. After appended with a 16-bit CRC, a rate-1/3tail-biting convolutional coding, 4× repetitions and QPSK modulation areapplied to the 40-bit codeword. The resulting QPSK symbol stream istransmitted across 4 subframes spread over 4 radio frames. Other thandetecting MIB, blind detection of the number of CRS ports is also neededfor PBCH.

However, the two-stage cell ID detection via PSS (1 out of 3 hypotheses)and SSS (1 out of 168 hypotheses) in LTE system suffers from the falsealarm issue especially for neighboring cell search. The UE ends updetecting many false cell ID candidates and needs PBCH detection toremove the false candidates. Moreover, for NR, the transmissionbandwidth containing synchronization signals is supposed to be largerthan LTE system, such that a new design of NR synchronization signals,aiming for robustness against initial frequency offset andauto-correlation profile, is possible.

This disclosure focuses on the design of NR synchronization signals,termed the NR-SS including NR-PSS and NR-SSS. Some of the embodimentsare also related to NR broadcast signals and channels, termed theNR-PBCH.

The present disclosure relates generally to wireless communicationsystems and, more specifically, to the design of NR synchronizationsignals, along with their associated mapping and procedures. NRsynchronization signals, termed the NR-SS, include NR-PSS and NR-SSS inthe present disclosure.

In some embodiments of component I, the functionality of PSS is toprovide coarse time domain and frequency domain synchronization, as wellas part of the physical cell ID detection. The PSS is constructed from afrequency-domain Zadoff-Chu (ZC) sequence of length 63, with the middleelement truncated to avoid using the d.c. subcarrier. 3 roots areselected for PSS to represent the 3 physical layer identities withineach group of cells. The PSS is transmitted in the central 6 resourceblocks (RBs), invariant to the system bandwidth to enable the UE tosynchronize without a priori information of the system bandwidth.

For NR, one of the basic functionalities of NR-PSS is still to providecoarse time domain and frequency domain synchronization, and thefrequency location of NR-PSS can still be independent from the systembandwidth. However, other functionalities and designs of the sequencecan be different from LTE system in the following aspects. Note that anycombination of the following aspects is covered in the presentdisclosure.

In one embodiment of NR-PSS sequence type: the NR-PSS sequence can stilluse at least one of the ZC sequences as in LTE system; and the NR-PSSsequence can use at least one of other sequences with the constantamplitude zero autocorrelation (CAZAC) property, for example,generalized ZC sequences as defined in some embodiments of componentIII.

In one embodiment of NR-PSS sequence length, the sequence length ofNR-PSS can be based on the available number of resourceelements/subcarriers for NR-PSS transmission within a SS block. In oneexample, if the synchronization transmission bandwidth is 5 MHz with 60kHz subcarrier spacing, or 10 MHz with 120 kHz subcarrier spacing, or 20MHz with 240 kHz subcarrier spacing, or 40 MHz with 480 kHz subcarrierspacing, or 80 MHz with 960 kHz subcarrier spacing, the available numberof resource elements can be up to N_(RE)=72, then if NR-PSS occupies thewhole synchronization transmission bandwidth, the NR-PSS sequence lengthL_(PSS) can be up to L_(PSS)≤N_(RE)=72, e.g. L_(PSS)=61 or 63, and ifNR-PSS occupies part of the transmission bandwidth to be multiplexedwith other signals (e.g. NR-SSS, and/or NR-PBCH, and/or repetition ofNR-PSS, and or zero sequence), the NR-PSS sequence length can be up to36 (for occupying half of the REs, e.g. L_(PSS)=23 or 29), or 24 (foroccupying one third of the REs, e.g. L_(PSS)=13 or 17) or 18 (foroccupying quarter of the REs, e.g. L_(PSS)=11 or 13).

In another example, if the synchronization transmission bandwidth is 5MHz with 30 kHz subcarrier spacing, or 10 MHz with 60 kHz subcarrierspacing, or 20 MHz with 120 kHz subcarrier spacing, or 40 MHz with 240kHz subcarrier spacing, or 80 MHz with 480 kHz subcarrier spacing, theavailable number of resource elements can be up to N_(RE)=144, then ifNR-PSS occupies the whole synchronization transmission bandwidth, theNR-PSS sequence length L_(PSS) can be up to L_(PSS)≤N_(RE)=144, e.g.L_(PSS)=127 or 131 or 133, and if NR-PSS occupies part of thetransmission bandwidth to be multiplexed with other signals (e.g.NR-SSS, and/or NR-PBCH, and/or repetition of NR-PSS, and/or zerosequence), the NR-PSS sequence length L_(PSS) can be up to N_(RE)/2=72(for occupying half of the REs, e.g. L_(PSS)=61 or 63) or N_(RE)/3=48(for occupying one third of the REs, e.g. L_(PSS)=37 or 39 or 41) or 36(for occupying quarter of the REs, e.g. L_(PSS)=23 or 29).

In yet another example, if the synchronization transmission bandwidth is5 MHz with 15 kHz subcarrier spacing, or 10 MHz with 30 kHz subcarrierspacing, or 20 MHz with 60 kHz subcarrier spacing, or 40 MHz with 120kHz subcarrier spacing, or 80 MHz with 240 kHz subcarrier spacing, theavailable number of resource elements can be up to N_(RE)=288, then ifNR-PSS occupies the whole synchronization transmission bandwidth, theNR-PSS sequence length L_(PSS) can be up to L_(PSS)≤N_(RE)=288, e.g.L_(PSS)=255, or 263 or 271, and if NR-PSS occupies part of thetransmission bandwidth to be multiplexed with other signals (e.g.NR-SSS, and/or NR-PBCH, and/or repetition of NR-PSS, and/or zerosequence), the NR-PSS sequence length can be up to 144 (for occupyinghalf of the REs, e.g. L_(PSS)=127 or 131 or 133) or 96 (for occupyingone third of the REs, e.g. L_(PSS)=79 or 83) or 72 (for occupyingquarter of the REs, e.g. L_(PSS)=61 or 63).

In yet another example, if the synchronization transmission bandwidth is20 MHz with 30 kHz subcarrier spacing, or 10 MHz with 15 kHz subcarrierspacing, the available number of resource elements can be up toN_(RE)=576, then if NR-PSS occupies the whole synchronizationtransmission bandwidth, the NR-PSS sequence length L_(PSS) can be up toL_(PSS)≤N_(RE)=576, e.g. L_(PSS)=571 or 569, and if NR-PSS occupies partof the transmission bandwidth to be multiplexed with other signals (e.g.NR-SSS, and/or NR-PBCH, and/or repetition of NR-PSS, and/or zerosequence), the NR-PSS sequence length can be up to 288 (for occupyinghalf of the REs, e.g. L_(PSS)=255 or 263 or 271) or 192 (for occupyingone third of the REs, e.g. L_(PSS)=191 or 187 or 181) or 144 (foroccupying quarter of the REs, e.g. L_(PSS)=127 or 131 or 133).

In yet another example, if the synchronization transmission bandwidth is20 MHz with 15 kHz subcarrier spacing, the available number of resourceelements can be up to N_(RE)=1152, then if NR-PSS occupies the wholesynchronization transmission bandwidth, the NR-PSS sequence lengthL_(PSS) can be up to L_(PSS); N_(RE)=1152, e.g. L_(PSS)=1151 or 1147,and if NR-PSS occupies part of the transmission bandwidth to bemultiplexed with other signals (e.g. NR-SSS, and/or NR-PBCH, and/orrepetition of NR-PSS, and/or zero sequence), the NR-PSS sequence lengthcan be up to 576 (for occupying half of the REs, e.g. L_(PSS)=571 or569) or 384 (for occupying one third of the REs, e.g. L_(PSS)=383 or379) or 192 (for occupying quarter of the REs, e.g. L_(PSS)=191 or 187or 181).

In some embodiments of time-domain or frequency-domain mapping, theNR-PSS sequence is mapped in frequency domain, which means the NR-PSSsequence is mapped across the resource elements or subcarriers infrequency domain, as in LTE system.

In one embodiment, the NR-PSS is mapped in time domain, which means theNR-PSS sequence is mapped across the OFDM samples in time domain.

In some embodiments of occupying the whole or part of thesynchronization transmission bandwidth, the NR-PSS sequence can occupyall the resource elements available in frequency domain within thedefined transmission bandwidth for NR-SS.

In one embodiment, the NR-PSS can only occupy part of the resourceelements available in frequency domain within the defined transmissionbandwidth for NR-SS (other signals like NR-SSS and/or NR-PBCH and/orNR-PSS's repetition and/or zero sequence can be multiplexedand/interleaved in the frequency domain as well).

In some embodiments of whether to include part of the physical cell ID,the indication of physical cell ID can be combined with other systemparameters, e.g. CP type (normal CP or extended CP if supported) ornumerology of data multiplexed with synchronization signals (see someembodiments of component VI).

In one embodiment, the NR-PSS sequence includes part of the physicalcell IDs, as in LTE system. For example, if utilizing the ZC-sequencesfor NR-PSS, multiple roots corresponding to the number of part of thephysical cell IDs are needed.

In another embodiment, the NR-PSS sequence includes no physical cell IDinformation, and the whole cell ID information is included in NR-SSS.Then, no hypothesis corresponding to the part of cell IDs is needed inthe construction of NR-PSS, and NR-PSS is purely utilized for coarsetiming and frequency domain offset acquisition.

In some embodiments of carrier frequency dependent or independent, theNR-PSS sequence can be common for all carrier frequencies supported inNR. For example, the design of NR-PSS is common for both >6 GHz systemand <6 GHz system. In one embodiment, the NR-PSS sequence can bedifferent for/dependent on the carrier frequency utilized in the system.For example, the design NR-PSS can be different for >6 GHz system and <6GHz system.

In some embodiments of numerology dependent or independent (notenumerology means subframe duration, sub-carrier spacing, cyclic prefixlength, transmission bandwidth, and/or any combination of these signalparameters), the NR-PSS sequence can be common/independent for allnumerologies supported. For example, for a given range of carrierfrequencies, if multiple numerologies are supported, NR-PSS has a commondesign using the default numerology chosen from the supportednumerologies. In another embodiment, the NR-PSS sequence can bedifferent for/dependent on the numerology adopted by the system. Forexample, for a given range of carrier frequencies, if multiplenumerologies are supported, NR-PSS has a different design for each ofthe supported numerologies.

Combinations of the aforementioned embodiments are supported in thispresent disclosure. Examples of NR-PSS sequences showing the combinationof above aspects are illustrated in TABLE 1, and other possiblecombinations are not excluded in the present disclosure. Note thatsystems within the same cell in the left column can use the same ordifferent NR-PSS sequence in the right column. Systems supportingmultiple numerologies (systems with the same carrier frequency andtransmission bandwidth but different subcarrier spacing, correspondingto different cells within different rows in the left column in TABLE 1)can use a common NR-PSS sequence according the default numerology or anumerology-specific NR-PSS sequence listed in the right column. Alsonote that, the number of NR-PSS sequences (e.g. one ZC-sequence ormultiple ZC-sequences) only refers to the number of sequences indicatingpart of the cell ID, and the number of NR-PSS sequences indicating othersystem parameters e.g. CP type (normal CP or extended CP if supported)or numerology of data multiplexed with synchronization signals, isdiscussed in some embodiments of component VI.

TABLE 1 NR-PSS sequence design Systems NR-PSS Sequence Design Examples<6 GHz carrier frequency with 5 One ZC-sequence with only one root(M_(PSS) = 1, no cell- MHz synchronization ID information) and lengthL_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 127 transmission bandwidth and 30 or131 or 133), which is mapped across the middle L_(PSS) − kHz subcarrierspacing 1 (e.g. 126 or 130 or 132) subcarriers (middle element ortruncated) within the N_(RE) = 144 subcarriers available for <6 GHzcarrier frequency with 20 the NR-PSS transmission in the frequencydomain, where MHz synchronization the NR-PSS is not multiplexed withother signals in the transmission bandwidth and 120 frequency domain.kHz subcarrier spacing One ZC-sequence with only one root (M_(PSS) = 1,no cell- or ID information) and length L_(PSS) ≤ κ_(PSS) · N_(RE), whichis >6 GHz carrier frequency with 40 mapped across the middle L_(PSS) − 1subcarriers (middle MHz synchronization element truncated) within theκ_(PSS) · N_(RE) subcarriers transmission bandwidth and 240 availablefor the NR-PSS transmission in the frequency kHz subcarrier spacingdomain, where the NR-PSS is multiplexed/interleaved or with othersignals (e.g. NR-SSS and/or NR-PBCH and/or >6 GHz carrier frequency with80 repetition of NR-PSS and/or zero sequence) within the SS MHzsynchronization block (NR-PSS occupies ratio κ_(PSS) of the transmissiontransmission bandwidth and 480 bandwidth, e.g. if κ_(PSS) = 0.5, thenNR-PSS sequence kHz subcarrier spacing length is no longer than κ_(PSS)· N_(RE) =72, and L_(PSS) = 61 (maximum number of or 63; if κ_(PSS) =0.33, then NR-PSS sequence length is no REs/subcarriers for NR-PSSlonger than κ_(PSS) · N_(RE) = 48, and L_(PSS) = 37 or 39 or 41; iftransmission N_(RE) = 144) κ_(PSS) = 0.25, then NR-PSS sequence lengthis no longer than κ_(PSS) · N_(RE) = 36, and L_(PSS) = 23 or 29). One ofthe ZC-sequences with M_(PSS) > 1 number of roots (M_(PSS) correspondsto the number of the part of the cell IDs included in NR-PSS) and lengthL_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 127 or 131 or 133), which is mappedacross the middle L_(PSS) − 1 (e.g. 126 or 130 or 132) subcarriers(middle element truncated) within the N_(RE) = 144 subcarriers availablefor the NR-PSS transmission in the frequency domain, where the NR-PSS isnot multiplexed with other signals in the frequency domain. One of theZC-sequences with M_(PSS) > 1 number of roots (M_(PSS) corresponds tothe number of the part of the cell IDs included in NR-PSS) lengthL_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped across the middle L_(PSS) −1 subcarriers (middle element truncated) within the κ_(PSS) · N_(RE)subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is multiplexed/interleaved with other signals(e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSS and/or zerosequence) within the SS block (NR-PSS occupies ratio κ_(PSS) of thetransmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSS sequencelength is no longer than κ_(PSS) · N_(RE) = 72, and L_(PSS) = 61 or 63;if κ_(PSS) = 0.33, then NR-PSS sequence length is no longer than κ_(PSS)· N_(RE) = 48, and L_(PSS) = 37 or 39 or 41; if κ_(PSS) = 0.25, thenNR-PSS sequence length is no longer than κ_(PSS) · N_(RE) = 36, andL_(PSS) = 23 or 29). One generalized ZC sequence (see some embodimentsof component III) with only one root (M_(PSS) = 1, no cell-IDinformation) and length L_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 127 or 131 or133), which is mapped across the middle L_(PSS) − 1 (e.g. 126 or 130 or132) subcarriers (middle element truncated) within the N_(RE) = 144subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is not multiplexed with other signals in thefrequency domain. One generalized ZC sequence (see some embodiments ofcomponent III) with only one root (M_(PSS) = 1, no cell-ID information)and length L_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped across the middleL_(PSS) − 1 subcarriers (middle element truncated) within the κ_(PSS) ·N_(RE) subcarriers available for the NR-PSS transmission in thefrequency domain, where the NR-PSS is multiplexed/interleaved with othersignals (e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSS and/orzero sequence) within the SS block (NR-PSS occupies ratio κ_(PSS) of thetransmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSS sequencelength is no longer than κ_(PSS) · N_(RE) = 72, and L_(PSS) = 61 or 63;if κ_(PSS) = 0.33, then NR-PSS sequence length is no longer than κ_(PSS)· N_(RE) = 48, and L_(PSS) = 37 or 39 or 41; if κ_(PSS) = 0.25, thenNR-PSS sequence length is no longer than κ_(PSS) · N_(RE) = 36, andL_(PSS) = 23 or 29). One of the generalized ZC sequences (see someembodiments of component III) with M_(PSS) > 1 number of roots (M_(PSS)corresponds to the number of the part of the cell IDs included inNR-PSS) and length L_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 127 or 131 or 133),which is mapped across the middle L_(PSS) − 1 (e.g. 126 or 130 or 132)subcarriers (middle element truncated) within the N_(RE) = 144subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is not multiplexed with other signals in thefrequency domain. One of the generalized ZC sequences (see someembodiments of component III) with M_(PSS) > 1 number of roots (Mpsscorresponds to the number of the part of the cell IDs included inNR-PSS) length L_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped across themiddle L_(PSS) − 1 subcarriers (middle element truncated) within theκ_(PSS) · N_(RE) subcarriers available for the NR-PSS transmission inthe frequency domain, where the NR-PSS is multiplexed/interleaved withother signals (e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSSand/or zero sequence) within the SS block (NR-PSS occupies ratio κ_(PSS)of the transmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSSsequence length is no longer than κ_(PSS) · N_(RE) = 72, and L_(PSS) =61 or 63; if κ_(PSS) = 0.33, then NR- PSS sequence length is no longerthan κ_(PSS) · N_(RE) = 48, and L_(PSS) = 37 or 39 or 41; if κ_(PSS)=0.25, then NR-PSS sequence length is no longer than κ_(PSS) · N_(RE) =36, and L_(PSS) = 23 or 29). <6 GHz carrier frequency with 5 OneZC-sequence with only one root (M_(PSS) = 1, no cell- MHzsynchronization ID information) and length L_(PSS) ≤ N_(RE) (e.g.L_(PSS) = 61 or transmission bandwidth and 60 63), which is mappedacross the middle L_(PSS) − 1 (e.g. 60 kHz subcarrier spacing or 62)subcarriers (middle element truncated) within the or N_(RE) = 72subcarriers available for the NR-PSS <6 GHz carrier frequency with 20transmission in the frequency domain, where the NR-PSS MHzsynchronization is not multiplexed with other signals in the frequencytransmission bandwidth and 240 domain. kHz subcarrier spacing One of theZC-sequences with M_(PSS) > 1 number of roots or (M_(PSS) corresponds tothe number of the part of the cell IDs >6 GHz carrier frequency with 40included in NR-PSS) and length L_(PSS) ≤ N_(RE) (e.g. L_(PSS) = MHzsynchronization 61 or 63), which is mapped across the middle L_(PSS) − 1transmission bandwidth and 480 (e.g. 60 or 62) subcarriers (middleelement truncated) kHz subcarrier spacing within the N_(RE) = 72subcarriers available for the NR-PSS or transmission in the frequencydomain, where the NR-PSS >6 GHz carrier frequency with 80 is notmultiplexed with other signals in the frequency MHz synchronizationdomain. transmission bandwidth and 960 One generalized ZC-sequence (seesome embodiments of kHz subcarrier spacing component III) with only oneroot (M_(PSS) = 1, no cell-ID (maximum number of information) and lengthL_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 61 or REs/subcarriers for NR-PSS 63),which is mapped across the middle L_(PSS) − 1 (e.g. 60 transmissionN_(RE) = 72) or 62) subcarriers (middle element truncated) within theN_(RE) = 72 subcarriers available for the NR-PSS transmission in thefrequency domain, where the NR-PSS is not multiplexed with other signalsin the frequency domain. One of the generalized ZC-sequences (see someembodiments of component III) with M_(PSS) > 1 number of roots (M_(PSS)corresponds to the number of the part of the cell IDs included inNR-PSS) and length L_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 61 or 63), which ismapped across the middle L_(PSS) − 1 (e.g. 60 or 62) subcarriers (middleelement truncated) within the N_(RE) = 72 subcarriers available for theNR-PSS transmission in the frequency domain, where the NR-PSS is notmultiplexed with other signals in the frequency domain. <6 GHz carrierfrequency with 5 One ZC-sequence with only one root (M_(PSS) = 1, nocell- MHz synchronization ID information) and length L_(PSS) ≤ N_(RE)(e.g. L_(PSS) = 255 transmission bandwidth and 15 or 263 or 271), whichis mapped across the middle L_(PSS) − kHz subcarrier spacing 1 (e.g. 254or 262 or 270) subcarriers (middle element or truncated) within theN_(RE) = 288 subcarriers available for <6 GHz carrier frequency with 20the NR-PSS transmission in the frequency domain, where MHzsynchronization the NR-PSS is not multiplexed with other signals in thetransmission bandwidth and 60 frequency domain. kHz subcarrier spacingOne ZC-sequence with only one root (M_(PSS) = 1, no cell- or IDinformation) and length L_(PSS) ≤ κ_(PSS) · N_(RE), which is >6 GHzcarrier frequency with 40 mapped across the middle L_(PSS) − 1subcarriers (middle MHz synchronization element truncated) within theκ_(PSS) · N_(RE) subcarriers transmission bandwidth and 120 availablefor the NR-PSS transmission in the frequency kHz subcarrier spacingdomain, where the NR-PSS is multiplexed/interleaved or with othersignals (e.g. NR-SSS and/or NR-PBCH and/or >6 GHz carrier frequency with80 repetition of NR-PSS and/or zero sequence) within the SS MHzsynchronization block (NR-PSS occupies ratio κ_(PSS) of the transmissiontransmission bandwidth and 240 bandwidth, e.g. if κ_(PSS) = 0.5, thenNR-PSS sequence kHz subcarrier spacing length is no longer than κ_(PSS)· N_(RE) = 144, and L_(PSS) = (maximum number of 127 or 131 or 133; ifκ_(PSS) = 0.33, then NR-PSS sequence REs/subcarriers for NR-PSS lengthis no longer than κ_(PSS) · N_(RE) = 96, and L_(PSS) = 79 transmissionN_(RE) = 288) or 83; if κ_(PSS) = 0.25, then NR-PSS sequence length isno longer than κ_(PSS) · N_(RE) = 72, and L_(PSS) = 61 or 63). One ofthe ZC-sequences with M_(PSS) > 1 number of roots (M_(PSS) correspondsto the number of the part of the cell IDs included in NR-PSS) and lengthL_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 255 or 263 or 271), which is mappedacross the middle L_(PSS) − 1 (e.g. 254 or 262 or 270) subcarriers(middle element truncated) within the N_(RE) = 288 subcarriers availablefor the NR-PSS transmission in the frequency domain, where the NR-PSS isnot multiplexed with other signals in the frequency domain. One of theZC-sequences with M_(PSS) > 1 number of roots (Mpss corresponds to thenumber of the part of the cell IDs included in NR-PSS) and lengthL_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped across the middle L_(PSS) −1 subcarriers (middle element truncated) within the κ_(PSS) · N_(RE)subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is multiplexed/interleaved with other signals(e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSS and/or zerosequence) within the SS block (NR-PSS occupies ratio κ_(PSS) of thetransmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSS sequencelength is no longer than κ_(PSS) · N_(RE) = 144, and L_(PSS) = 127 or131 or 133; if κ_(PSS) = 0.33, then NR-PSS sequence length is no longerthan κ_(PSS) · N_(RE) = 96, and L_(PSS) = 79 or 83; if κ_(PSS) = 0.25,then NR-PSS sequence length is no longer than κ_(PSS) · N_(RE) = 72, andL_(PSS) = 61 or 63). One generalized ZC-sequence (see some embodimentsof component III) with only one root (M_(PSS) = 1, no cell-IDinformation) and length L_(PSS) ≤ κ_(PSS) (e.g. L_(PSS) = 255 or 263 or271), which is mapped across the middle L_(PSS) − 1 (e.g. 254 or 262 or270) subcarriers (middle element truncated) within the N_(RE) = 288subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is not multiplexed with other signals in thefrequency domain. One generalized ZC-sequence (see some embodiments ofcomponent III) with only one root (M_(PSS) = 1, no cell-ID information)and length L_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped across the middleL_(PSS) − 1 subcarriers (middle element truncated) within the κ_(PSS) ·N_(RE) subcarriers available for the NR-PSS transmission in thefrequency domain, where the NR-PSS is multiplexed/interleaved with othersignals (e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSS and/orzero sequence) within the SS block (NR-PSS occupies ratio κ_(PSS) of thetransmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSS sequencelength is no longer than κ_(PSS) · N_(RE) = 144, and L_(PSS) = 127 or131 or 133; if κ_(PSS) = 0.33, then NR-PSS sequence length is no longerthan κ_(PSS) · N_(RE) = 96, and L_(PSS) = 79 or 83; if κ_(PSS) = 0.25,then NR-PSS sequence length is no longer than κ_(PSS) · N_(RE) = 72, andL_(PSS) = 61 or 63). One of the generalized ZC-sequences (see someembodiments of component III) with M_(PSS) > 1 number of roots (M_(PSS)corresponds to the number of the part of the cell IDs included inNR-PSS) and length L_(PSS) ≤ N_(RE) (e.g. L_(PSS) = 255 or 263 or 271),which is mapped across the middle L_(PSS) − 1 (e.g. 254 or 262 or 270)subcarriers (middle element truncated) within the N_(RE) = 288subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-PSS is not multiplexed with other signals in thefrequency domain. One of the generalized ZC-sequences (see someembodiments of component III) with M_(PSS) > 1 number of roots (M_(PSS)corresponds to the number of the part of the cell IDs included inNR-PSS) and length L_(PSS) ≤ κ_(PSS) · N_(RE), which is mapped acrossthe middle L_(PSS) − 1 subcarriers (middle element truncated) within theκ_(PSS) · N_(RE) subcarriers available for the NR-PSS transmission inthe frequency domain, where the NR-PSS is multiplexed/interleaved withother signals (e.g. NR-SSS and/or NR-PBCH and/or repetition of NR-PSSand/or zero sequence) within the SS block (NR-PSS occupies ratio κ_(PSS)of the transmission bandwidth, e.g. if κ_(PSS) = 0.5, then NR-PSSsequence length is no longer than κ_(PSS) · N_(RE) = 144, and L_(PSS) =127 or 131 or 133; if κ_(PSS) = 0.33, then NR-PSS sequence length is nolonger than κ_(PSS) · N_(RE) = 96, and L_(PSS) = 79 or 83; if κ_(PSS) =0.25, then NR-PSS sequence length is no longer than κ_(PSS) · N_(RE) =72, and L_(PSS) = 61 or 63).

In some embodiments of component II, the functionality of SSS sequenceis to detect the other part of cell ID based on the coarse time-domainand frequency-domain synchronization detection from PSS. CP size andduplexing mode information are also detected by SSS. The construction ofSSS sequences are based on the maximum length sequences (also known asM-sequences). Each SSS sequence is constructed by interleaving twolength-31 BPSK modulated subsequences in frequency domain, where the twosubsequences are constructed from the same M-sequence using differentcyclic shifts. The cyclic shift indices for both parts are functions ofthe physical cell ID group.

For NR, the basic functionalities of NR-SSS remain to detect the cell IDor part of the cell ID, as well as CP size and duplexing mode ifsupported in NR. However, with respective to the details of the designof NR-SSS, the following aspects can be considered. Note that thecombinations of aspects are supported in this disclosure.

In some embodiments of NR-SSS sequence type, the NR-SSS sequence canstill use the combination of two interleaved M-sequences as in LTEsystem. In another embodiment, the NR-SSS sequence can use ZC-sequenceswherein a set of ZC sequences with different root indices and/or cyclicshifts are utilized. In yet another embodiment, the NR-SSS can use othersequences with the constant amplitude zero autocorrelation (CAZAC)property, for example, generalized ZC sequences as defined in someembodiments III. In yet another embodiment, the NR-SSS can beconstructed by channel coding (possibly with a cyclic redundancy check(CRC)) with rate matching (see some embodiments component IV).

In some embodiments of NR-SSS sequence length, the sequence length ofNR-PSS can be based on the available number of resourceelements/subcarriers for NR-SSS transmission within a SS block. Thelength of NR-SSS can be either the same as NR-PSS, or different fromNR-PSS. In one example, if the synchronization transmission bandwidth is5 MHz with 60 kHz subcarrier spacing, or 10 MHz with 120 kHz subcarrierspacing, or 20 MHz with 240 kHz subcarrier spacing, or 40 MHz with 480kHz subcarrier spacing, or 80 MHz with 960 kHz subcarrier spacing, theavailable number of resource elements can be up to N_(RE)=72, then ifNR-SSS occupies the whole synchronization transmission bandwidth, theNR-SSS sequence length L_(SSS) can be up to L_(SSS); N_(RE)=72, e.g.L_(SSS)=61 or 63, and if NR-PSS occupies part of the transmissionbandwidth to be multiplexed/interleaved with other signals (e.g. NR-PSS,and/or NR-PBCH, and/or repetition of NR-SSS, and/or zero sequence), theNR-SSS sequence length L_(SSS) can be up to 36 (for occupying half ofthe REs, e.g. L_(SSS)=23 or 29) or 24 (for occupying one third of theREs, e.g. L_(SSS)=13 or 17) or 18 (for occupying quarter of the REs,e.g. L_(SSS)=11 or 13).

In another example, if the synchronization transmission bandwidth is 5MHz with 30 kHz subcarrier spacing, or 10 MHz with 60 kHz subcarrierspacing, or 20 MHz with 120 kHz subcarrier spacing, or 40 MHz with 240kHz subcarrier spacing, or 80 MHz with 480 kHz subcarrier spacing, theavailable number of resource elements can be up to N_(RE)=144, then ifNR-SSS occupies the whole synchronization transmission bandwidth, theNR-SSS sequence length L_(SSS) can be up to L_(SSS)≤N_(RE)=144, e.g.L_(SSS)=127 or 131 or 133, and if NR-SSS occupies part of thetransmission bandwidth to be multiplexed/interleaved with other signals(e.g. NR-PSS, and/or NR-PBCH, and/or repetition of NR-SSS, and/or zerosequence), the NR-SSS sequence length L_(SSS) can be up to N_(RE)/2=72(for occupying half of the REs, e.g. L_(SSS)=61 or 63) or N_(RE)/3=48(for occupying one third of the REs, e.g. L_(SSS)=37 or 39 or 41) or 36(for occupying quarter of the REs, e.g. L_(SSS)=23 or 29).

In yet another example, if the synchronization transmission bandwidth is5 MHz with 15 kHz subcarrier spacing, or 10 MHz with 30 kHz subcarrierspacing, or 20 MHz with 60 kHz subcarrier spacing, or 40 MHz with 120kHz subcarrier spacing, or 80 MHz with 240 kHz subcarrier spacing, theavailable number of resource elements can be up to N_(RE)=288, then ifNR-PSS occupies the whole synchronization transmission bandwidth, theNR-SSS sequence length L_(SSS) can be up to L_(PSS)≤N_(RE)=288, e.g.L_(SSS)=255 or 263 or 271, and if NR-SSS occupies part of thetransmission bandwidth to be multiplexed/interleaved with other signals(e.g. NR-PSS, and/or NR-PBCH, and/or repetition of NR-SSS, and/or zerosequence), the NR-SSS sequence length can be up to 144 (for occupyinghalf of the REs, e.g. L_(SSS)=127 or 131 or 133) or 96 (for occupyingone third of the REs, e.g. L_(SSS)=79 or 83) or 72 (for occupyingquarter of the REs, e.g. L_(SSS)=61 or 63).

In yet another example, if the synchronization transmission bandwidth is20 MHz with 30 kHz subcarrier spacing, the available number of resourceelements can be up to N_(RE)=576, then if NR-SSS occupies the wholesynchronization transmission bandwidth, the NR-PSS sequence lengthL_(SSS) can be up to L_(SSS)≤N_(RE)=576, e.g. L_(SSS)=571 or 569, and ifNR-PSS occupies part of the transmission bandwidth to bemultiplexed/interleaved with other signals (e.g. NR-PSS, and/or NR-PBCH,and/or repetition of NR-SSS, and/or zero sequence), the NR-SSS sequencelength can be up to 288 (for occupying half of the REs, e.g. L_(SSS)=255or 263 or 271) or 192 (for occupying one third of the REs, e.g.L_(SSS)=191 or 187 or 181) or 144 (for occupying quarter of the REs,e.g. L_(SSS)=127 or 131 or 133).

In yet another example, if the synchronization transmission bandwidth is20 MHz with 15 kHz subcarrier spacing, the available number of resourceelements can be up to N_(RE)=1152, then if NR-SSS occupies the wholesynchronization transmission bandwidth, the NR-SSS sequence lengthL_(SSS) can be up to L_(SSS)≤N_(RE)=1152, e.g. L_(SSS)=1151 or 1147, andif NR-SSS occupies part of the transmission bandwidth to bemultiplexed/interleaved with other signals (e.g. NR-PSS, and/or NR-PBCH,and/or repetition of NR-SSS, and/or zero sequence), the NR-SSS sequencelength can be up to 576 (for occupying half of the REs, e.g. L_(SSS)=571or 569) or 384 (for occupying one third of the bandwidth, e.g.L_(SSS)=383 or 379) or 192 (for occupying quarter of the bandwidth, e.g.L_(SSS)=191 or 187 or 181).

In some embodiments of time-domain or frequency-domain mapping, theNR-SSS sequence is mapped in frequency domain, which means the NR-SSSsequence is mapped across the resource elements or subcarriers infrequency domain, as in LTE system. In another embodiment, the NR-SSS ismapped in time domain, which means the NR-SSS sequence is mapped acrossthe OFDM samples in time domain.

In some embodiments of occupying the whole or part of thesynchronization transmission bandwidth, the NR-SSS sequence can occupyall the resource elements available in frequency domain within thedefined transmission bandwidth for NR-SS. In another embodiment, theNR-SSS can only occupy part of the resource elements available infrequency domain within the defined transmission bandwidth for NR-SS(other signals like NR-PSS and/or NR-PBCH and/or NR-SSS's repetition canbe multiplexed in the frequency domain as well).

In some embodiments of whether to include part of or entire physicalcell ID, the NR-SSS sequence includes part of the physical cell IDs, asin LTE system. For example, NR-SSS carries the cell ID information notincluded in NR-PSS. In another embodiment, the NR-SSS sequence includesthe entire physical cell ID information.

In some embodiments of Carrier frequency dependent or independent, theNR-SSS sequence can be common for all carrier frequencies supported inNR. For example, the design of NR-SSS is common for both >6 GHz systemand <6 GHz system. In another embodiment, the NR-SSS sequence can bedifferent for/dependent on the carrier frequency utilized in the system.For example, the design NR-SSS can be different for >6 GHz system and <6GHz system.

In some embodiments of numerology dependent or independent (notenumerology means subframe duration, sub-carrier spacing, cyclic prefixlength, transmission bandwidth, and/or any combination of these signalparameters), the NR-SSS sequence can be common/independent for allnumerologies supported. For example, for a given range of carrierfrequencies, if multiple numerologies are supported, NR-SSS has a commondesign using the default numerology chosen from the supportednumerologies. In another embodiment, the NR-SSS sequence can bedifferent for/dependent on the numerology adopted by the system. Forexample, for a given range of carrier frequencies, if multiplenumerologies are supported, NR-SSS has a different design for each ofthe supported numerologies.

In some embodiments of indication of transmission timing of NR-SS withinthe SS burst set, e.g. including subframe index and/or symbol indexwithin a radio frame, transmission timing of NR-SS within the SS burstset can be detected from the NR-SSS sequence by adding hypotheses inaddition to the cell ID (e.g. performing additional scramblingsequences). In another embodiment, transmission timing of NR-SS withinthe SS burst set can be detected from the NR-SSS sequence by decodingthe transport block directly if the construction of NR-SSS sequence isbased on coding (see some embodiments of component IV). In yet anotherembodiment, part of the transmission timing of NR-SS within the SS burstset is indicated by NR-SSS sequence (either explicitly or implicitly),and the remaining timing information is indicated by othersignals/channels. In yet another embodiment, no transmission timing ofNR-SS within the SS burst set is indicated by NR-SSS sequence.

In some embodiments of relation to the NR-PSS, the transmissionbandwidth occupied by the NR-SSS can be the same as NR-PSS. In anotherembodiment, the transmission bandwidth occupied by the NR-SSS can bedifferent from NR-PSS. In yet another embodiment, the SS block where theNR-SSS is transmitted can be the same as NR-PSS. In yet anotherembodiment, the SS block where the NR-SSS is transmitted can bedifferent from NR-PSS (NR-PSS and NR-SSS can be transmitted in differentSS blocks within a SS burst).

Note that some aspects on NR-SSS sequences can be related to/dependenton the aspects of NR-PSS sequences. For example, if NR-PSS contains partof the cell ID, NR-SSS only contains the other part of the cell ID, andif NR-PSS contains no cell ID information, NR-SSS contains the entirecell ID information. The other aspects on NR-SSS and NR-PSS can beunrelated or independent. For example, the design of sequence type andsequence length of NR-PSS and NR-SSS can be independent, either the sameor different.

Also note that the aspects on NR-SSS sequence can be related. Forexample, if NR-SSS is constructed using channel coding and ratematching, transmission timing of NR-SS within the SS block can beexplicitly adding extra information bits before encoding, and if NR-SSSis constructed using family of sequences with particular property (e.g.M-sequence, ZC-sequence, or other sequence with CAZAC property),transmission timing of NR-SS within the SS block can rely on addingextra number of hypotheses in addition to the cell ID.

Combinations of the aforementioned embodiments are supported in thisdisclosure. NR-SSS sequences showing the combination of above aspectsare illustrated in TABLE 2, and other possible combinations are notexcluded in the disclosure. Note that systems within the same cell inthe left column can use the same or different NR-SSS sequence in theright column. Systems supporting multiple numerologies (systems with thesame carrier frequency and transmission bandwidth but differentsubcarrier spacing, corresponding to different cells within differentrows in the left column in TABLE 2) can use a common NR-SSS sequenceaccording the default numerology or a numerology-specific NR-SSSsequence listed in the right column. TABLE 2 only shows example withmaximum number of REs/subcarriers for NR-PSS transmission N_(RE)=144,and design for NR-SSS sequences in other systems with other value of themaximum number of subcarriers can be scaled (e.g. scale the sequencelength and number of subcarriers mapped for NR-SSS) based on the one inTABLE 2, similar to the scaling method as shown in TABLE 1 for thedesign of NR-PSS.

TABLE 2 NR-SSS sequence design Systems NR-SSS Sequence Design Examples<6 GHz carrier frequency with 5 A sequence with length L_(SSS) = 2 ·L_(M) is a combination of MHz synchronization two M-sequences, eachM-sequence with length L_(M) (e.g. transmission bandwidth and 30 L_(M) =63 or 65 or 66), which is mapped across the middle kHz subcarrierspacing 2 · L_(M) (e.g. 126 or 130 or 132) subcarriers within the orN_(RE) = 144 subcarriers available for the NR-SSS 6 GHz carrierfrequency with 10 transmission in the frequency domain, where the NR-SSSMHz synchronization is not multiplexed with other signals in thefrequency transmission bandwidth and 60 domain. Up to L_(M) · L_(M)(e.g. 3969 or 4225 or 4356) kHz subcarrier spacing hypotheses aresupported by this NR-SSS sequence to or cover up to C_(SSS) ≤ L_(M) ·L_(M)/2 cell IDs (e.g. C_(SSS) = 504 <6 GHz carrier frequency with or1008 cell IDs assuming no cell ID information in NR- 20 MHzsynchronization PSS), if 2 possible locations of NR-SSS transmissionstransmission bandwidth and 120 needs to be indicated within a SS burst;and to cover up kHz subcarrier spacing to C_(SSS) ≤ L_(M) · L_(M) cellIDs (e.g. C_(SSS) = 504 or 1008 or (maximum number of 2016 cell IDsassuming no cell ID information in NR- REs/subcarriers for NR-SSS PSS),if only one possible location of NR-SSS transmission N_(RE) = 144, notransmission is supported within a SS burst (no beam sweeping)indication). A sequence with length L_(SSS) = 2 · L_(M) is a combinationof two M-sequences, each M-sequence with length L_(M), which is mappedacross the middle 2 · L_(M) subcarriers within the κ_(SSS) · N_(RE)subcarriers available for the NR- SSS transmission in the frequencydomain, where the NR-SSS is multiplexed with other signals (e.g. NR-PSSand/or NR-PBCH and/or repetition of NR-SSS) in the frequency domain. Forexample, κ_(SSS) = 0.5, L_(M) = 30 or 31, then up to L_(M) · L_(M) (e.g.900 or 961) hypotheses are supported by this NR-SSS sequence to cover upto C_(SSS) ≤ L_(M) · L_(M)/2 cell IDs (e.g. C_(SSS) = 168 or 336 cellIDs assuming part of cell ID information in NR-PSS), if 2 possiblelocations of NR-SSS transmissions needs to be indicated within a SSburst; and to cover up to C_(SSS) ≤ L_(M) · L_(M) cell IDs (e.g. C_(SSS)= 168 or 336 or 672 cell IDs assuming part of cell ID information inNR-PSS), if only one possible location of NR-SSS transmission issupported within a SS burst (no indication). One of the ZC-sequenceswith 1 < M_(SSS) ≤ L_(SSS) − 1 (e.g. M_(SSS) = 126) different root indexand/or S_(SSS) ≥ 1 (S_(SSS) = 5 or 10) cyclic shifts and length L_(SSS)≤ N_(RE) (e.g. L_(SSS) = 127 or 131 or 133), which is mapped across themiddle L_(SSS) − 1 subcarriers (middle element truncated) within theN_(RE) = 144 subcarriers available for the NR-PSS transmission in thefrequency domain, where the NR-PSS is not multiplexed with other signalsin the frequency domain. Up to M_(SSS) · S_(SSS) hypotheses aresupported by this NR-SSS sequence to cover up to C_(SSS) ≤ M_(SSS) ·S_(SSS)/2 cell IDs (e.g. C_(SSS) = 504 cell IDs assuming no cell IDinformation in NR-PSS), if 2 possible locations of NR- SSS transmissionsneeds to be indicated within a SS burst; and to cover up to C_(SSS) ≤M_(SSS) · S_(SSS)/2 cell IDs (e.g. C_(SSS) = 504 or 1008 cell IDsassuming no cell ID information in NR-PSS), if only one possiblelocation of NR-SSS transmission is supported within a SS burst (noindication). One of the ZC-sequences with 1 < M_(SSS) ≤ L_(SSS) − 1different root index and/or S_(SSS) ≥ 1 cyclic shifts and length L_(SSS)≤ N_(RE), which is mapped across the middle L_(SSS) − 1 subcarriers(middle element truncated) within the κ_(SSS) · N_(RE) subcarriersavailable for the NR-SSS transmission in the frequency domain, where theNR-SSS is multiplexed with other signals (e.g. NR-PSS and/or NR-PBCHand/or repetition of NR-SSS) in the frequency domain. For example,κ_(SSS) = 0.5, L_(SSS) = 31, M_(SSS) = 30, S_(SSS) = 12, then up toM_(SSS) · S_(SSS) (e.g. 480) hypotheses are supported by this NR-SSSsequence to cover up to C_(SSS) ≤ M_(SSS) · S_(SSS)/2 cell IDs (e.g.C_(SSS) = 168 cell IDs assuming part of cell ID information in NR-PSS),if 2 possible locations of NR-SSS transmissions needs to be indicatedwithin a SS burst; and to cover up to C_(SSS) ≤ M_(SSS) · S_(SSS) cellIDs (e.g. C_(SSS) = 168 or 336 cell IDs assuming part of cell IDinformation in NR-PSS), if only one possible location of NR-SSStransmission is supported within a SS burst (no indication). One of thegeneralized ZC-sequences (see some embodiments of component III) with 1< M_(SSS) ≤ L_(SSS) − 1 (e.g. M_(SSS) = 126) different root index and/orS_(SSS) ≥ 1 (S_(SSS) = 5 or 10) cyclic shifts and length L_(SSS) ≤N_(RE) (e.g. L_(SSS) = 127 or 131 or 133), which is mapped across themiddle L_(SSS) − 1 subcarriers (middle element truncated) within theN_(RE) = 144 subcarriers available for the NR- PSS transmission in thefrequency domain, where the NR-PSS is not multiplexed with other signalsin the frequency domain. Up to M_(SSS) · S_(SSS) hypotheses aresupported by this NR-SSS sequence to cover up to C_(SSS) ≤ M_(SSS) ·S_(SSS)/2 cell IDs (e.g. C_(SSS) = 504 cell IDs assuming no cell IDinformation in NR-PSS), if 2 possible locations of NR-SSS transmissionsneeds to be indicated within a SS burst; and to cover up to C_(SSS) ≤M_(SSS) · S_(SSS)/2 cell IDs (e.g. C_(SSS) = 504 or 1008 cell IDsassuming no cell ID information in NR-PSS), if only one possiblelocation of NR-SSS transmission is supported within a SS burst (noindication). One of the generalized ZC-sequences (see some embodimentsof component III) with 1 < M_(SSS) ≤ L_(SSS) − 1 different root indexand/or S_(SSS) ≥ 1 cyclic shifts and length L_(SSS) ≤ N_(RE), which ismapped across the middle L_(SSS) − 1 subcarriers (middle elementtruncated) within the κ_(SSS) · N_(RE) subcarriers available for theNR-SSS transmission in the frequency domain, where the NR-SSS ismultiplexed with other signals (e.g. NR-PSS and/or NR-PBCH and/orrepetition of NR-SSS) in the frequency domain. For example, κ_(SSS) =0.5, L_(SSS) = 31, M_(SSS) = 30, S_(SSS) = 12, then up to M_(SSS) ·S_(SSS) (e.g. 480) hypotheses are supported by this NR-SSS sequence tocover up to C_(SSS) ≤ M_(SSS) · S_(SSS)/2 cell IDs (e.g. C_(SSS) = 168cell IDs assuming part of cell ID information in NR-PSS), if 2 possiblelocations of NR-SSS transmissions needs to be indicated within a SSburst; and to cover up to C_(SSS) ≤ M_(SSS) · S_(SSS) cell IDs (e.g.C_(SSS) = 168 or 336 cell IDs assuming part of cell ID information inNR-PSS), if only one possible location of NR-SSS transmission issupported within a SS burst (no indication). A sequence with lengthL_(SSS) is constructed by coding from a transport block with at least Anumber of bits (see some embodiments of component IV), which is mappedacross the middle L_(SSS) − 1 subcarriers (middle element truncated)within the N_(RE) = 144 subcarriers available for the NR-PSStransmission in the frequency domain, where the NR-PSS is notmultiplexed with other signals in the frequency domain. For example, A =10, L_(SSS) = 126 or 130, then the NR-SSS can cover up to 504 cell IDsand 2 possible locations of NR-SSS transmissions needs to be indicatedwithin a SS burst, or cover up to 1008 cell IDs and only one possiblelocation of NR-SSS transmission is supported within a SS burst (noindication). A sequence with length L_(SSS) is constructed by codingfrom a transport block with at least A number of bits (see someembodiments of component V), which is mapped across the middle L_(SSS) −1 subcarriers (middle element truncated) within the κ_(SSS) · N_(RE)subcarriers available for the NR-PSS transmission in the frequencydomain, where the NR-SSS is multiplexed with other signals (e.g. NR- PSSand/or NR-PBCH and/or repetition of NR-SSS) in the frequency domain. Forexample, κ_(SSS) = 0.5, A = 9, L_(SSS) = 60 or 62, then the NR-SSS cancover up to 168 cell IDs and 2 possible locations of NR-SSStransmissions needs to be indicated within a SS burst, or cover up to336 cell IDs and only one possible location of NR-SSS transmission issupported within a SS burst (no indication). >6 GHz carrier frequencywith A sequence with length L_(SSS) = 2 · L_(M) is a combination of 40MHz synchronization two M-sequences, each M-sequence with length L_(M)(e.g. transmission bandwidth and 240 L_(M) = 63 or 65 or 66), which ismapped across the middle kHz subcarrier spacing 2 · L_(M) (e.g. 126 or130 or 132) subcarriers within the or N_(RE) = 144 subcarriers availablefor the NR-SSS >6 GHz carrier frequency with transmission in thefrequency domain, where the NR-SSS 80 MHz synchronization is notmultiplexed with other signals in the frequency transmission bandwidthand 480 domain. Up to L_(M) · L_(M) (e.g. 3969 or 4225 or 4356) kHzsubcarrier spacing hypotheses are supported by this NR-SSS sequence to(maximum number of cover up to C_(SSS) ≤ L_(M) · L_(M)/N_(B) cell IDs(e.g. C_(SSS) = 168 REs/subcarriers for NR-SSS cell IDs assuming part ofcell ID information in NR-PSS), transmission N_(RE) = 144, beam if N_(B)= 14 beams for NR-SSS transmissions needs to be sweeping on N_(B)indicated within a SS burst. directions/beams) A sequence with lengthL_(SSS) = 2 · L_(M) is a combination of two M-sequences, each M-sequencewith length L_(M), which is mapped across the middle 2 · L_(M)subcarriers within the κ_(SSS) · N_(RE) subcarriers available for theNR- SSS transmission in the frequency domain, where the NR-SSS ismultiplexed with other signals (e.g. NR-PSS and/or NR-PBCH and/orrepetition of NR-SSS) in the frequency domain. For example, κ_(SSS) =0.5, L_(M) = 30 or 31, then up to L_(M) · L_(M) (e.g. 900 or 961)hypotheses are supported by this NR-SSS sequence to cover up to C_(SSS)≤ L_(M) · L_(M)/N_(B) cell IDs (e.g. C_(SSS) = 84 cell IDs assuming partof cell ID information in NR-PSS), if N_(B) = 7 beams for NR-SSStransmissions needs to be indicated within a SS burst. One of theZC-sequences with 1 < M_(SSS) ≤ L_(SSS) − 1 (e.g. M_(SSS) = 126)different root index and/or S_(SSS) ≥ 1 (S_(SSS) = 20) cyclic shifts andlength L_(SSS) ≤ N_(RE) (e.g. L_(SSS) = 127 or 131 or 133), which ismapped across the middle L_(SSS) − 1 subcarriers (middle elementtruncated) within the N_(RE) = 144 subcarriers available for the NR-PSStransmission in the frequency domain, where the NR-PSS is notmultiplexed with other signals in the frequency domain. Up to M_(SSS) ·S_(SSS) hypotheses are supported by this NR-SSS sequence to cover up toC_(SSS) ≤ M_(SSS) · S_(SSS)/N_(B) cell IDs (e.g. C_(SSS) = 168 cell IDsassuming part of cell ID information in NR-PSS), if N_(B) = 14 beams forNR-SSS transmissions needs to be indicated within a SS burst. One of theZC-sequences with 1 < M_(SSS) ≤ L_(SSS) − 1 different root index and/orS_(SSS) ≥ 1 cyclic shifts and length L_(SSS) ≤ N_(RE), which is mappedacross the middle L_(SSS) − 1 subcarriers (middle element truncated)within the κ_(SSS) · N_(RE) subcarriers available for the NR-SSStransmission in the frequency domain, where the NR-SSS is multiplexedwith other signals (e.g. NR-PSS and/or NR-PBCH and/or repetition ofNR-SSS) in the frequency domain. For example, κ_(SSS) = 0.5, L_(SSS) =31, M_(SSS) = 30, S_(SSS) = 20, then up to M_(SSS) · S_(SSS) (e.g. 600)hypotheses are supported by this NR-SSS sequence to cover up to C_(SSS)≤ M_(SSS) · S_(SSS)/N_(B) cell IDs (e.g. C_(SSS) = 84 cell IDs assumingpart of cell ID information in NR-PSS), if N_(B) = 7 beams for NR-SSStransmissions needs to be indicated within a SS burst. One of thegeneralized ZC-sequences (see some embodiments of component III) with 1< M_(SSS) ≤ L_(SSS) − 1 (e.g. M_(SSS) = 126) different root index and/orS_(SSS) ≥ 1 (S_(SSS) = 20) cyclic shifts and length L_(SSS) ≤ N_(RE)(e.g. L_(SSS) = 127 or 131 or 133), which is mapped across the middleL_(SSS) − 1 subcarriers (middle element truncated) within the N_(RE) =144 subcarriers available for the NR- PSS transmission in the frequencydomain, where the NR-PSS is not multiplexed with other signals in thefrequency domain. Up to M_(SSS) · S_(SSS) hypotheses are supported bythis NR-SSS sequence to cover up to C_(SSS) ≤ M_(SSS) · S_(SSS)/N_(B)cell IDs (e.g. C_(SSS) = 168 cell IDs assuming part of cell IDinformation in NR-PSS), if N_(B) = 14 beams for NR-SSS transmissionsneeds to be indicated within a SS burst. One of the generalizedZC-sequences (see some embodiments of component III) with 1 < M_(SSS) ≤L_(SSS) − 1 different root index and/or S_(SSS) ≥ 1 cyclic shifts andlength L_(SSS) ≤ N_(RE), which is mapped across the middle L_(SSS) − 1subcarriers (middle element truncated) within the κ_(SSS) · N_(RE)subcarriers available for the NR-SSS transmission in the frequencydomain, where the NR-SSS is multiplexed with other signals (e.g. NR-PSSand/or NR-PBCH and/or repetition of NR-SSS) in the frequency domain. Forexample, κ_(SSS) = 0.5, L_(SSS) = 31, M_(SSS) = 30, S_(SSS) = 20, thenup to M_(SSS) · S_(SSS) (e.g. 600) hypotheses are supported by thisNR-SSS sequence to cover up to C_(SSS) ≤ M_(SSS) · S_(SSS)/N_(B) cellIDs (e.g. C_(SSS) = 84 cell IDs assuming part of cell ID information inNR-PSS), if N_(B) = 7 beams for NR-SSS transmissions needs to beindicated within a SS burst. A sequence with length L_(SSS) isconstructed by coding from a transport block with at least A number ofbits (see some embodiments of component IV), which is mapped across themiddle L_(SSS) − 1 subcarriers (middle element truncated) within theN_(RE) = 144 subcarriers available for the NR-PSS transmission in thefrequency domain, where the NR-PSS is not multiplexed with other signalsin the frequency domain. For example, A = 13, L_(SSS) = 126 or 130, thenthe NR-SSS can cover up to 504 cell IDs and N_(B) = 14 beams for NR-SSStransmissions needs to be indicated within a SS burst. A sequence withlength L_(SSS) is constructed by coding from a transport block with atleast A number of bits (see some embodiments of component IV), which ismapped across the middle L_(SSS) − 1 subcarriers (middle elementtruncated) within the κ_(SSS) · N_(RE) subcarriers available for theNR-PSS transmission in the frequency domain, where the NR-SSS ismultiplexed with other signals (e.g. NR- PSS and/or NR-PBCH and/orrepetition of NR-SSS) in the frequency domain. For example, κ_(SSS) =0.5, A = 13, L_(SSS) = 60 or 62, then the NR-SSS can cover up to 504cell IDs and N_(B) = 14 beams for NR-SSS transmissions needs to beindicated within a SS burst. <6 GHz carrier frequency with 5 A sequencewith length L_(SSS) = 2 · L_(M) is a combination of MHz synchronizationtwo interleaved M-sequences, each M-sequence with transmission bandwidthand 15 length L_(M) (e.g. L_(M) = 127), which is mapped across the kHzsubcarrier spacing middle 2 · L_(M) (e.g. 254) subcarriers within theN_(RE) = or 288 subcarriers available for the NR-SSS transmission in <6GHz carrier frequency with the frequency domain, where the NR-SSS is not10 MHz synchronization multiplexed with other signals in the frequencydomain transmission bandwidth and 30 within the synchronizationtransmission bandwidth. Up to kHz subcarrier spacing L_(M) · L_(M) (e.g.16129) hypotheses are supported by this or NR-SSS sequence to cover upto C_(SSS) ≤ L_(M) · L_(M)/N_(b) cell <6 GHz carrier frequency with IDs(e.g. C_(SSS) = 504 or 1008), if N_(b) possible locations of 20 MHzsynchronization NR-SSS transmissions needs to be indicated; or to covertransmission bandwidth and 60 up to C_(SSS) ≤ L_(M) · L_(M) cell IDs(e.g. C_(SSS) = 504 or 1008), kHz subcarrier spacing if no SS blocktiming indication is not combined with cell or ID indication (e.g.through further scrambling in NR-SSS >6 GHz carrier frequency with orusing other signals/channels) . . . For example, for single- 40 MHzsynchronization beam system, if NR-SS periodicity is 5 ms, N_(b) = 2timing transmission bandwidth and 120 hypotheses need to be indicated byNR-SSS. For another kHz subcarrier spacing example, for multi-beamsystem, there can be N_(b) number or of timing hypotheses need to beindicated by NR-SSS, <6 GHz carrier frequency with where N_(b) issmaller than or equal to the number of SS 80 MHz synchronization blockindex within a SS burst set. transmission bandwidth and 240 kHzsubcarrier spacing (maximum number of REs/subcarriers for NR-PSStransmission N_(RE) = 288) <6 GHz carrier frequency with 5 A sequencewith length L_(SSS) = 2 · L_(M) is a combination of MHz synchronizationtwo interleaved M-sequences, each M-sequence with transmission bandwidthand 30 length L_(M) (e.g. L_(M) = 63), which is mapped across the kHzsubcarrier spacing middle 2 · L_(M) (e.g. 126) subcarriers within theN_(RE) = or 144 subcarriers available for the NR-SSS transmission in <6GHz carrier frequency with the frequency domain, where the NR-SSS is not10 MHz synchronization multiplexed with other signals in the frequencydomain transmission bandwidth and 60 within the synchronizationtransmission bandwidth. Up to kHz subcarrier spacing L_(M) · L_(M) (e.g.3969) hypotheses are supported by this NR- or SSS sequence to cover upto C_(SSS) ≤ L_(M) · L_(M)/N_(b) cell IDs <6 GHz carrier frequency with(e.g. C_(SSS) = 504 or 1008), if N_(b) possible locations of NR- 20 MHzsynchronization SSS transmissions needs to be indicated; or to cover upto transmission bandwidth and 120 C_(SSS) ≤ L_(M) · L_(M) cell IDs (e.g.C_(SSS) = 504 or 1008), if no kHz subcarrier spacing SS block timingindication is not combined with cell ID or indication (e.g. throughfurther scrambling in NR-SSS or >6 GHz carrier frequency with usingother signals/channels). For example, for single- 40 MHz synchronizationbeam system, if NR-SS periodicity is 5 ms, N_(b) = 2 timing transmissionbandwidth and 240 hypotheses need to be indicated by NR-SSS. For anotherkHz subcarrier spacing example, for multi-beam system, there can beN_(b) number or of timing hypotheses need to be indicated by NR-SSS, <6GHz carrier frequency with where N_(b) is smaller than or equal to thenumber of SS 80 MHz synchronization block index within a SS burst set.transmission bandwidth and 480 kHz subcarrier spacing (maximum number ofREs/subcarriers for NR-PSS transmission N_(RE) = 144)

In some embodiments of component III, ZC sequences are used in thedesign of PSS, preamble of random access channel (PRACH), soundingreference signals (SRS), etc. ZC sequences belong to the class ofpoly-phase sequences (each term being a complex root of unity) withideal cyclic autocorrelation (CAZAC property), having at the same timeoptimal cross-correlation, which means that the lower bound on themaximum magnitude of the periodic cross-correlation can be achieved.

ZC sequences {a_(k,r)} of length L_(ZC) and root r are defined asa_(k,r)=

$\{ {\begin{matrix}{W_{L_{ZC},r}^{\frac{k^{2}}{2} + {qk}},{k = 0},1,\ldots \;,{L_{ZC} - 1},{{if}\mspace{14mu} L_{ZC}\mspace{14mu} {is}\mspace{14mu} {even}}} \\{W_{L_{ZC},r}^{\frac{{k{({k + 1})}}^{2}}{2} + {qk}},{k = 0},1,\ldots \;,{L_{ZC} - 1},{{if}\mspace{14mu} L_{ZC}\mspace{14mu} {is}\mspace{14mu} {odd}}}\end{matrix}\quad} $

where q is any integer, and W_(n,r) is a primitive root of unity

${W_{n,r} = {\exp ( {- \frac{j\; 2\pi \; r}{n}} )}},$

r is any integer relatively prime to n, and 0<r<n.

For example, for the construction of SS sequence in LTE system, q is setto be 0, and root indices r=25, 29, 34 are chosen to indicate 3 physicallayer identities within each group of cells.

In NR, for the construction of the NR-PSS and NR-SSS sequences, at leastone of the sequences in a generalized class of poly-phase sequences withCAZAC property and optimal cross-correlation can be used, which is basedon ZC sequences {a_(k,r)} of length L_(ZC)=l·m² where l and m are anypositive integers. Let {b_(i)}, i=0, 1, . . . , m−1, be any complexsequence of absolute value 1. Then a generalized ZC sequence {s_(k,r)}with length L_(GZC) and root r is defined as s_(k,r)=a_(k,r)−b_(k mod m)for k=0, 1, . . . , L_(GZC)−1.

For example, {s_(k,r)} of length L_(GZC)=63 (e.g. l=7, and m=3) withroot r and q=0 is given by {b₀, b₁W_(63,r) ², b₂W_(63,r) ⁹, b₀W_(63,r)²⁴, . . . , b₁W_(63,r) ⁶², b₂}.

Note that if b_(i) is taken to be 1 for all i=0, 1, . . . , m−1, thenthe generalized ZC sequence of length L_(GZC) and root r reduces to theZC sequence of length L_(ZC)=L_(GZC) and root r. Also note that for somesequence length L_(GZC), there can be different pairs of (l, m) suchthat L_(GZC)=l·m², which results in different constructions of thegeneralized ZC sequence.

In one embodiment, the length of the generalized ZC sequence L_(GZC)=l·1where m is set to 1, then the generalized ZC sequence is a scaledversion of the ZC sequence, i.e., s_(k,r)=b₀·a_(k,r).

In another embodiment, the length of the generalized ZC sequenceL_(GZC)=1·m², where l is set to 1, then the resulting sequencecorresponds to the so called Frank sequence which is widely used inspread-spectrum wireless communications.

In yet another embodiment, the length of the generalized ZC sequenceL_(GZC)=l·2², where m is set to 2, and the {b_(i)} sequence can bechosen to be b₀=1, b₁=−1.

In yet another embodiment, {b_(i)} is taken to be

$\exp ( {- \frac{j\; 2\pi \; \overset{\_}{f}}{N_{FFT}}} )$

for all i=0, 1, . . . , m−1, where f is the average of the frequencyoffset range, and N_(FFT) is the size of the FFT for OFDM.

In one embodiment, the generalized ZC sequences can be utilized for theconstruction of NR-PSS. In another embodiment, the generalized ZCsequences with possibly cyclic shifts to increase the total number ofsupported hypotheses can be utilized for the construction of NR-SSS.

In one embodiment, the length of generalized ZC sequences L_(GZC) can bedetermined by the available number of resource elements/subcarriers infrequency domain for the transmission of NR-PSS and/or NR-SSS. Theconstructed NR-PSS and/or NR-SSS using generalized ZC sequences can bemapped across the middle L_(GZC)−1 subcarriers (middle elementtruncated) within the N_(RE) subcarriers available for the NR-PSS and/orNR-SSS transmission in the frequency domain.

In one example, if the available number of resource elements isN_(RE)=144 (e.g. 5 MHz with 30 kHz subcarrier spacing or 40 MHz with 240kHz subcarrier spacing), the length of generalized ZC sequences can be127 or 131 or 133.

In another example, if the available number of resource elements isN_(RE)=72 (e.g. 5 MHz with 60 kHz subcarrier spacing or 40 MHz with 480kHz subcarrier spacing), the length of generalized ZC sequences can be61 or 63.

In yet another example, if the available number of resource elements isN_(RE)=288 (e.g. 5 MHz with 15 kHz subcarrier spacing or 40 MHz with 120kHz subcarrier spacing), the length of generalized ZC sequences can be255 or 263 or 271.

In some embodiments of component IV, NR-SS and NR-PBCH, NR-PSS, NR-SSSand/or NR-PBCH can be transmitted within an SS block; one or multiple SSblock(s) compose an SS burst; one or multiple SS burst(s) compose an SSburst set. For example, the following alternatives can be considered.

FIG. 13 illustrates an example SS burst including an SS block 1300according to embodiments of the present disclosure. The embodiment ofthe SS burst including an SS block 1300 illustrated in FIG. 13 is forillustration only. FIG. 13 does not limit the scope of this disclosureto any particular implementation of the SS burst including an SS block1300.

In one embodiment of alternative 1, Each SS burst has only one SS block,and one SS burst compose an SS burst set as shown in FIG. 13. Note thatthe sequences transmitted in each SS block may or may not be the same.For example, in LTE system, two neighboring SS blocks are transmittedwithin one radio frame, and the SSS sequences are different.

FIG. 14 illustrates an example SS burst including multiplenon-successive SS blocks 1400 according to embodiments of the presentdisclosure. The embodiment of the SS burst including multiplenon-successive SS blocks 1400 illustrated in FIG. 14 is for illustrationonly. FIG. 14 does not limit the scope of this disclosure to anyparticular implementation of the SS burst including multiplenon-successive SS blocks 1400.

In one embodiment of alternative 2, each SS burst has multiplenon-successive SS blocks, and one or multiple SS burst(s) compose an SSburst set as shown in FIG. 14 giving an example of SS burst consistedfrom two SS blocks.

FIG. 15 illustrates an example SS burst including multiple successive SSblocks 1500 according to embodiments of the present disclosure. Theembodiment of the SS burst including multiple successive SS blocks 1500illustrated in FIG. 15 is for illustration only. FIG. 15 does not limitthe scope of this disclosure to any particular implementation of the SSburst including multiple successive SS blocks 1500.

In one embodiment of alternative 3, each SS burst has multiplesuccessive SS blocks, and one or multiple SS burst(s) compose an SSburst set as shown in FIG. 15. System with one burst of beam sweepingcan be considered as an example of this alternative.

FIG. 16 illustrates another example SS burst including multiplesuccessive SS blocks 1600 according to embodiments of the presentdisclosure. The embodiment of the SS burst including multiple successiveSS blocks 1600 illustrated in FIG. 16 is for illustration only. FIG. 16does not limit the scope of this disclosure to any particularimplementation of the SS burst including multiple successive SS blocks1600.

In one embodiment of alternative 4, each SS burst has multiplesuccessive SS blocks and the SS blocks can be divided into multiplenon-successive sub-bursts, and one or multiple SS burst(s) compose an SSburst set as shown in FIG. 16. System with multiple bursts of beamsweeping can be considered as an example of this alternative.

The coding-based (also referred as message-based) transmission of NR-SSScan utilize the following options for a given range of carrierfrequencies. In one embodiment of option 1, one or more transport blocksof NR-SSS is coded and mapped into the REs within a single SS block.This option can be utilized for all above alternatives (either above 6GHz systems with beam sweeping, or in below 6 GHz systems with no beamsweeping), where each of the transmission of NR-SSS within the SS blockis encoded separately. If the number of resource elements for thetransmission of NR-SSS within each SS block is denoted as N₁, and thenumber of bits for each symbol in the modulation scheme is denoted asN_(mod), then output from channel coding and rate matching hasE=N₁·N_(mod) bits. For example, each NR-SSS is transmitted using 62resource elements within a SS block, and the modulation scheme is QPSK,then E=124. For another example, each NR-SSS is transmitted using 126resource elements within a SS block, and the modulation scheme is QFSK,then E=252.

In one embodiment of option 2, one or more transport blocks of NR-SSS iscoded and mapped into the REs within multiple SS blocks, where the SSblocks have the same timing information within the SS burst (e.g.including subframe timing and symbol timing within a radio frame). Thisoption can be utilized for all above alternatives (either above 6 GHzsystems with beam sweeping, or in below 6 GHz systems with no beamsweeping), but the application to alternative 1 is the same as option 1if sequences transmitted in all SS blocks are the same. In this option,the NR-SSSs within multiple SS blocks can be jointly coded. If thenumber of resource elements for the transmission of NR-SSS within eachSS block is denoted as N₁, the number of SS blocks jointly coded for thesame transport block of NR-SSS is denoted as N₂, and the number of bitsfor each symbol in the modulation scheme is denoted as N_(mod), then theoutput from channel coding and rate matching has E=N₁·N₂·N_(mod) bits.Note that option 1 can be considered as a special case of option 2 withN₂=1. For example, each NR-SSS is transmitted using 62 resource elementswithin a SS block, four SS blocks are jointly coded (e.g., FIG. 15, forexample, the SS blocks with the same k are jointly coded (1≤k≤K)), andthe modulation scheme is QPSK, then E=496. Note that the number of SSblocks to be jointly coded does not necessarily equal to the number ofSS bursts within a SS burst set.

In one embodiment of option 3, one or more transport blocks of NR-SSS iscoded and mapped into the REs within multiple SS blocks, where the SSblocks may not have the same timing information within the SS burst(e.g. including subframe timing and symbol timing within a radio frame).This option can be utilized for all above alternatives (either above 6GHz systems with beam sweeping, or in below 6 GHz systems with no beamsweeping), but the application to alternative 1 is the same as option 1and option 2 if sequences transmitted in all SS blocks are the same. Inthis option, the NR-SSSs within multiple SS blocks are jointly coded,but timing information cannot be part of the transport block of NR-SSS,since NR-SSS with different timing information cannot be jointly codedif transport block(s) of NR-SSS contains timing information. In thisoption, timing information can be transmitted explicitly using aseparate codeword in NR-SSS, or implicitly indicated by NR-SSS (e.g.introducing frequency offset or cyclic shifts to distinguish the SSblocks), or explicitly transmitted and/or implicitly indicated by othersignal/channels (e.g. NR-PBCH).

If the number of resource elements for the transmission of NR-SSS withineach SS block is denoted as N₁, the number of SS blocks jointly codedfor the same transport block of NR-SSS is denoted as N₂, and the numberof bits for each symbol in the modulation scheme is denoted as N_(mod),then output from channel coding and rate matching has E=N₁·N₂·N_(mod)bits. For example, each NR-SSS is transmitted using 62 resource elementswithin a SS block, four SS blocks are jointly coded, and the modulationscheme is QPSK, then E=496. Note that the number of SS blocks to bejointly coded in this option can be selected from any SS blocks withinthe SS burst set, for example all from the same burst, or all fromdifferent bursts within the burst set, or part from the same burst andthe rest from different bursts.

FIG. 17 illustrates a flow chart of NR-SSS construction 1700 accordingto embodiments of the present disclosure. The embodiment of the NR-SSSconstruction 1700 illustrated in FIG. 17 is for illustration only. FIG.17 does not limit the scope of this disclosure to any particularimplementation of the NR-SSS construction 1700.

General steps for construction of NR-SSS based on coding are shown inFIG. 17. This flowchart is applicable to all above options. Note thatmodules or part of the functionalities within the modules in the flowchart can be set as default values such that they do not have anyimpact.

The payload of physical cell ID contained in NR-SSS is denoted as n₁,where it may corresponds to the whole or part of the cell ID based onthe design of NR-PSS. For example, if the number of physical cell IDscontained in NR-SSS is 168 (e.g. as in LTE system), n=8. For anotherexample, if the number of physical cell IDs contained in NR-SSS is 504(all cell ID information is contained in NR-SSS), n₁=9. The number ofbits to indicate the timing information of NR-SSS transmitted within aSS burst set or within a radio frame (e.g. SS block index) is denoted asn₂ (where n₂≥0), e.g. including the subframe timing and/or symbol timingwithin a radio frame. For example, if only one SS block is transmittedwithin each SS burst set or radio frame, then n₂=0 (no need to code thisinformation). For another example, if two SS blocks are transmittedwithin each SS burst set or radio frame, then n₂=1. For yet anotherexample, if NR-SSS is transmitted in a beam seeping pattern for >6 GHzmulti-beam operation system, and the number of beam in each beamsweeping burst is 14, and if one radio frame or SS burst set only haveone SS burst, then n₂=4. If two bursts of beam sweeping are performed ina radio frame or SS burst set, then n₂=5. The number of reserved bitsfor other purpose is denoted as n₃, where n₃≥0.

In one embodiment, all the payload bits are encoded into a singlecodeword. Then, the total payload of transport block in NR-PSS beforeadding CRC is denoted as A(i)=n₁+n₂+n₃ and i=1, and the entire transportblock is denoted as a₀ ^((i)), . . . , a_(A(i)-1) ^((i)) (1701 as shownin FIG. 17).

In another embodiment, the payload bits indicating the cell ID and SSblock index are encoded separately to generate two codewords. Then, thetotal payloads of transport blocks in NR-SSS before adding CRC aredenoted as A(1)=n₁+n₃ ⁽¹⁾ and A(2)=n₂+n₃ ⁽²⁾ correspondingly (n₃ ⁽¹⁾+₃⁽²⁾=n₃), and each of the transport block is denoted as a₀ ^((i)), . . ., a_(A(i)-1) ^((i)), and i=1, 2 (1701 as shown in FIG. 17). The firstset of message bits can be common through different SS blocks, and canbe combined at the receiver across multiple received NR-SSSs; while thesecond set of message bits may be different across multiple SS blocks,and may not be combined at the receiver across multiple receivedNR-SSSs.

In yet another embodiment, part of the payload bits is encoded into asingle codeword. For example, SS block index is not encoded in thecodeword. Then, the total payload of transport block in NR-PSS beforeadding CRC is denoted as A(i)=n₁+n₃ and i=1, and the entire transportblock is denoted as a₀ ^((i)), . . . , a_(A(i)-1) ^((i)) (1701 as shownin FIG. 17). The rest information (e.g. SS block index information) canbe explicitly or implicitly indicated in other ways (e.g. usingdifferent frequency offset or cyclic shifts).

In CRC attachment module (1702 as shown in FIG. 17), the entiretransport block for each codeword is used to calculate the CRC paritybits, and the generated parity bits are denoted as p₀ ^((i)), . . . ,P_(L(i)-1) ^((i)). L(i) is the length of parity check bits, orequivalently the length of CRC, for each codeword. If there are multiplecodewords to be encoded (i>1), the L(i) can be the same or different foreach codeword. For instance, L(i) can equal to 0 (no CRC attachment), or8, or 16, or 24, and chosen independently for each codeword. For oneexample, L(1)=8 and L(2)=0. After the generation of CRC bits, a CRC maskx₀ ^((i)), . . . , x_(L(i)-1) ^((i)) can be utilized to scramble the CRCsequence according to the gNB transmit antenna configuration. The outputfrom scrambling is given by c₀ ^((i)), . . . , c_(K(i)-1) ^((i)) (1703as shown in FIG. 17), where c_(k) ^((i))=a_(k) ^((i)) for k=0, . . . ,A(i)−1, and c_(k)=(p_(k-A(i)) ^((i))+x_(k-A(i)) ^((i))) mod 2 fork=A(i), . . . , A(i)+L(i)−1. Note that by choosing x_(l) ^((i))=0 forall 0≤l≤L(i)−1, the scrambling procedure has no impact to the CRC bits.In one embodiment, the choice of CRC mask can be the same as the one forNR-PBCH for a particular number of transmit antenna ports.

The information bits input to the channel coding module (1704 as shownin FIG. 17) are denoted by c₀ ^((i)), . . . , c_(K(i)-1) ^((i)), whereC(i)=A(i)+L(i) denotes the number of information bits to be encoded forcodeword i. Channel coding codes can be utilized on the information bitsto generate the encoded codeword(s) d₀ ^((i)), . . . , d_(D(i)-1) ^((i))(1705 as shown in FIG. 17). One or multiple of the channel codingschemes can be utilized for this module. Note that if there are multiplecodewords to be encoded (i>1), the channel coding scheme can be the sameor different for each codeword.

In one example, Reed-Muller (RM) codes can be utilized to generate theencoded codeword, where D(i)>C(i) and C(i)/D(i) is the rate of RM codes.In another example, tail biting convolutional codes (TBCC) can beutilized to generate the encoded codeword, where D(i)=C(i) and threestreams of codes are output by the rate-1/3 TBCC encoder (encodedcodewords can be denoted as d₀ ^((i,s)), . . . , d_(D(i)-1) ^((i,s))where s=0, 1, 2). In yet another example, low-density parity-check(LDPC) codes can be utilized to generate the encoded codeword, whereD(i)>C(i) and C(i)/D(i) is the rate of LDPC codes. In yet anotherexample, polar codes can be utilized to generate the encoded codeword,where D(i)>C(i) and C(i)/D(i) is the rate of polar codes. In yet anotherexample, Turbo codes can be utilized to generate the encoded codeword,where D(i)=C(i) and three streams of codes are output by the rate-1/3Turbo encoder (encoded codewords can be denoted as d₀ ^((i,s)), . . . ,d_(D(i)-1) ^((i,s)) where s=0, 1, 2).

The encoded codeword(s) are delivered to the rate matching module (1706as shown in FIG. 17). d₀ ^((i)), . . . , d_(D(i)-1) ^((i)) or d₀^((is)), . . . , d_(D(i)-1) ^((i,s)) are repeated and/or truncated toconstruct a sequence with desired length. Then, interleaving (withoutusing cell ID to generate the interleaving index sequence) is performedif desired to generate the output sequence e₀, . . . , e_(E-1) or e₀^((i)), . . . , e_(E(i)-1) ^((i)) depending on whether multiplecodewords are combined in this module (1707 as shown in FIG. 17). Notethat the interleaving index sequence can be constructed such that noeffect of interleaving is performed (equivalent as no interleaving). Inone embodiment, if multiple codewords are encoded from previous modules,multiple codewords can be combined and rate matched and interleavedtogether. In another embodiment, if multiple codewords are encoded fromprevious modules, multiple codewords can be rate matched and interleavedseparately.

The block of bits e₀, . . . , e_(E-1) or e₀ ^((i)), . . . , e_(E(i)-1)^((i)) (depending on whether multiple codewords are combined in channelcoding module) are modulated (1308 as shown in FIG. 17), resulting in ablock of complex-valued modulation symbols d(0), . . . , d(M−1) ord^((i))(0), . . . , d^((i))(M(i)−1) depending on whether multiplecodewords are combined in channel coding module (1309 as shown in FIG.17), where M or M(i) is the number of symbols. If multiple codewords arenot combined, multiple codewords can be modulated separately using thesame or different modulation schemes. For one example, the modulationscheme for NR-SSS can be BPSK. For another example, the modulationscheme for NR-SSS can be QPSK. For yet another example, the modulationscheme for NR-SSS can be M-FSK. For still another example, themodulation scheme for NR-SSS can be OOK.

The block of modulation symbols may be mapped to layers and precoded(1710 as shown in FIG. 17), resulting in a block of vectors y^((p))(0),. . . , y^((p))(M−1) or y^((i,p))(0), . . . , y^((i,p))(M(i)−1), where0≤p≤P−1 and P is the number of ports for NR-SSS transmission (1711 asshown in FIG. 17). If multiple codewords are generated from previousmodules and not combined until this module, multiple codewords can becombined first in this module and then be mapped to layers and precodedjointly, or can be mapped to layers and precoded separately. In oneembodiment, the number of layer is set to 1 and precoding matric is anidentity matrix (equivalent as no layer mapping or precoding, and theinput and output of this module are identical). In another embodiment,the method for layer mapping and precoding can be according to themethod for layer mapping and precoding in LTE system specificationcorrespondingly. In yet another embodiment, if NR-SSS and NR-PBCH arejointly coded, the method for layer mapping and precoding can be thesame as the ones for NR-PBCH.

The block of complex-valued symbols y^((p))(0), . . . , y^((p))(M−1) ory^((i,p))(0), . . . , y^((i,p))(M(i)−1), for each antenna port p ismapped to the M resource elements available for NR-SSS transmission(1712 as shown in FIG. 17). If multiple streams of symbols are generatedfrom the preceding module, multiple codewords are combined in thismodule before mapping. The mapping to the resource elements (j, k) maybe in the increasing order of first the index j, then the index k inslot 1 in subframe 0 and finally the radio frame number.

In one embodiment, NR-SSS can be jointly coded with NR-PBCH. Forexample, the NR-SSS and NR-PBCH(s) within the same SS block (may or maynot be in the same symbol) can be jointly coded and mapped into the REsof the NR-SSS and NR-PBCH(s) correspondingly. FIG. 17 can still beutilized to illustrate the procedures for joint coding of NR-SSS andNR-PBCH(s), and the transport block and all sequences correspond to theones for NR-SSS and NR-PBCH(s). In one sub-embodiment, NR-SSS can bejointly coded with PBCH using one codeword. In another sub-embodiment,NR-SSS can be jointly coded with PBCH using multiple codewords (e.g.part of NR-SSS (cell ID) and NR-PBCH jointly coded, and the remaining ofNR-SSS (SS block index) coded separately, or NR-SSS coded in onecodeword, and NR-PBCH coded in another codeword). For example, thecommon message bits across SS blocks including cell ID and MIB inNR-PBCH can be coded using one codeword, and the SS block index orsymbol timing can be coded using a separate codeword such that signalcombination of multiple receiving of NR-SSS and NR-PBCH is possible atthe receiver.

In another embodiment, if NR-PBCH and NR-SSS are not jointly coded, theprinciple of multiple codewords in coding-based/message-basedconstruction method for NR-SSS can also be utilized for NR-PBCH. If theSS block index is explicitly indicated in NR-PBCH, the message bitscontaining the SS block index can be coded separately. The CRC bits andcoding rate of the message bits containing the SS block index can be thesame or different from the ones of regular message bits in NR-PBCH (e.g.needed system information or MIB). In one embodiment, the number of CRCbits can be 0 for SS block index (e.g. no CRC protection). In anotherembodiment, the number of CRC bits can be smaller than the one forregular message bits in NR-PBCH (e.g. smaller than 16 as used in LTEspecification). The motivation of using separate codewords for regularmessage bits in NR-PBCH and message bits for symbol index is to enablesignal combining of regular message bits for multiple receiving ofNR-PBCH.

In some embodiments of component V, SSS, PSS and PBCH are multiplexed intime domain, occupying the same bandwidth in frequency domain. For NR,the resource elements available for the transmission of NR-SSS, NR-PSS,and NR-PBCH can be at least equivalent to or larger than then ones forthe transmission of SSS, PSS, and PBCH in LTE specification. Theincrease of sources enables more complex mapping and multiplexingschemes for NR-SS and NR-PBCH, with potentially more accurate detectionand robust synchronization.

The followings are considered for the mapping and multiplexing of NR-SSand NR-PBCH. Note that the combinations of aspects are supported in thepresent disclosure.

In one embodiment of multiplexing in frequency domain or time domain,NR-PSS, NR-SSS and NR-PBCH can be multiplexed in time domain. Forexample, SSS, PSS, and PBCH are multiplexed in time domain andtransmitted in successive symbols as in LTE specification

In another embodiment, NR-PSS, NR-SSS and NR-PBCH can be multiplexed infrequency domain. For example, each of the NR-PSS, NR-SSS and NR-PBCHoccupied a predefined part of the transmission bandwidth and transmittedusing the same symbol duration. In yet another embodiment, NR-PSS,NR-SSS and NR-PBCH can be multiplexed in a hybrid pattern consisted ofboth time domain and frequency domain multiplexing.

In one embodiment of carrier frequency dependent or independent, themapping and/or multiplexing of NR-PSS, NR-SSS and NR-PBCH within in eachSS block can be the same for all the range of carrier frequenciessupported in NR. For example, NR utilizes the same mapping and/ormultiplexing of NR-PSS, NR-SSS and NR-PBCH within in each SS block forall supported carrier frequencies.

In another embodiment, the mapping and multiplexing NR-PSS, NR-SSS andNR-PBCH within in each SS block can be different for a given range ofcarrier frequencies supported in NR. For example, NR utilizes one schemeof mapping and multiplexing of NR-PSS, NR-SSS and NR-PBCH for systemswith carrier frequency >6 GHz, and utilizes another scheme of mappingand multiplexing of NR-PSS, NR-SSS and NR-PBCH for systems with carrierfrequency <6 GHz.

In one embodiment of numerology dependent or independent (notenumerology means subframe duration, sub-carrier spacing, cyclic prefixlength, transmission bandwidth, and/or any combination of these signalparameters), if multiple numerologies are supported for a given range ofcarrier frequencies, the mapping and multiplexing of NR-PSS, NR-SSS andNR-PBCH can be different for a given numerology.

In another embodiment, if multiple numerologies are supported for agiven range of carrier frequencies, the mapping and multiplexing ofNR-PSS, NR-SSS and NR-PBCH can be common for all the supportednumerologies (e.g. choosing a design scheme based on the defaultnumerology). In yet another embodiment, if multiple numerologies aresupported for a given range of carrier frequencies, the NR-PSS, NR-SSS,and NR-PBCH may utilize different numerologies to generate a commonmapping and multiplexing scheme.

In one embodiment of repetition of NR-PSS, and/or NR-SSS, and/orNR-PBCH, NR-PSS, and/or NR-SSS, and/or NR-PBCH can be repeated once ormore than once in time domain and/or frequency domain within each SSblock. The replicate(s)/copies of NR-PSS, and/or NR-SSS, and/or NR-PBCHessentially carry the same information as the original one(s), and canbe exactly the same or cyclic shifted and/or interleaved. In onesub-embodiment, each of the replicate(s)/copies of NR-PSS, and/orNR-SSS, and/or NR-PBCH can be multiplexed with a unique phase shift(e.g. one of the DFT phase shifts).

In one embodiment of interleaving of NR-PSS, and/or NR-SSS, and/orNR-PBCH in frequency domain, if NR-PSS, and/or NR-SSS, and/or NR-PBCH,and/or their replicates (if applicable) are multiplexed in frequencydomain within the same symbol, the sequences can be interleaved in thefrequency domain. In one sub-embodiment, NR-PSS, and/or NR-SSS, and/orNR-PBCH can be interleaved with an empty sequence, such that a combstructure is utilized in frequency domain (equivalent as time domainrepetition within an OFDM symbol). For example, if two copies ofNR-PSS/NR-SSS/NR-PBCH are concatenated in frequency domain within oneOFDM symbol, one of them can be multiplied by −1 before concatenation.For another example, if N copies of NR-PSS/NR-SSS/NR-PBCH areconcatenated in frequency domain within one OFDM symbol, N copies ofNR-PSS/NR-SSS/NR-PBCH can be multiplied by e^(jn·2π/N) or e^(−jn·2π/N),where 0≤n≤N−1, correspondingly.

In one embodiment of same or different mapping and multiplexing acrossSS blocks, the mapping and/or multiplexing of NR-PSS, and/or NR-SSS,and/or NR-PBCH within SS blocks are the same. For example, LTEspecification has the same mapping and multiplexing for all SS blocks.In another embodiment, the mapping and/or multiplexing of NR-PSS, and/orNR-SSS, and/or NR-PBCH within SS blocks can be different. For example,only NR-PSS is transmitted in one SS block, and NR-SSS and NR-PBCH aretransmitted in the next SS block. For another example, only NR-PSS andNR-SSS are transmitted in one SS block, and NR-PSS, NR-SSS and NR-PBCHare transmitted in the next SS block.

FIG. 18A illustrate an example combination of mapping and multiplexing1800 according to embodiments of the present disclosure. The embodimentof the combination of mapping and multiplexing 1800 illustrated in FIG.18A is for illustration only. FIG. 18A does not limit the scope of thisdisclosure to any particular implementation of the combination ofmapping and multiplexing 1800.

FIG. 18B illustrates another example combination of mapping andmultiplexing 1850 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 1850illustrated in FIG. 18B is for illustration only. FIG. 18B does notlimit the scope of this disclosure to any particular implementation ofthe combination of mapping and multiplexing 1850.

FIG. 18C illustrates yet another example combination of mapping andmultiplexing 1870 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 1870illustrated in FIG. 18C is for illustration only. FIG. 18C does notlimit the scope of this disclosure to any particular implementation ofthe combination of mapping and multiplexing 1870.

FIG. 19A illustrates yet another example combination of mapping andmultiplexing 1900 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 1900illustrated in FIG. 19A is for illustration only. FIG. 19A does notlimit the scope of this disclosure to any particular implementation ofthe combination of mapping and multiplexing 1900.

FIG. 19B illustrates yet another example combination of mapping andmultiplexing 1950 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 1950illustrated in FIG. 19B is for illustration only. FIG. 19B does notlimit the scope of this disclosure to any particular implementation ofthe combination of mapping and multiplexing 1950.

FIG. 19C illustrates yet another example combination of mapping andmultiplexing 1970 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 1970illustrated in FIG. 19C is for illustration only. FIG. 19C does notlimit the scope of this disclosure to any particular implementation ofthe combination of mapping and multiplexing 1970.

FIG. 20 illustrates yet another example combination of mapping andmultiplexing 2000 according to embodiments of the present disclosure.The embodiment of the combination of mapping and multiplexing 2000illustrated in FIG. 20 is for illustration only. FIG. 20 does not limitthe scope of this disclosure to any particular implementation of thecombination of mapping and multiplexing 2000.

Examples showing the mapping and multiplexing design within each SSblock with aspect to the combination of above aspects are illustrated inFIGS. 18A-C, 19A-C, 20, and other possible combinations are not excludedin the disclosure. In the relationship of NR-PSS, NR-SSS, and NR-PBCH isfor illustration purpose only, and the following notes are pointed out.

The duration of NR-PBCH may be one or more symbols when multiplexing intime domain, although it appears to be the same length as NR-PSS orNR-SSS for simplicity in the figures. When multiplexing multiple signalsincluding NR-PSS, NR-SSS, NR-PBCH and their possible replicates in timedomain, their neighboring relationship in time domain can be exchanged,although the figures show only one possible alignment of the signals.

When multiplexing multiple signals including NR-PSS, NR-SSS, NR-PBCH andtheir possible replicates in frequency domain, their neighboringrelationship in frequency domain can be exchanged, although the figuresshow only one possible alignment of the signals. When multiplexingmultiple signals including NR-PSS, NR-SSS, NR-PBCH and multiplexingmultiple signals' possible replicates in time domain, multiplexingmultiple signals are necessary to be in the successive symbols. Therecan be gap between the signals in time domain within a SS block.

As shown in FIG. 18A, 1801, 1802 and 1803 are examples of transmittingrepetition of the NR-PSS, NR-SSS, and NR-PBCH in time domain within a SSblock, correspondingly. 1804, 1805, and 1806 are examples oftransmitting repetition of the NR-PSS, NR-SSS, and NR-PBCH in frequencydomain within a SS block, correspondingly.

As shown in FIG. 18B, 1807 is an example of interleaving of the NR-PSS,NR-SSS, and NR-PBCH in frequency domain within a SS block (1807 can alsobe combined with 1804, 1805, and 1806 to support repetition andinterleaving at the same time in frequency domain). 1808 is an exampleof multiplexing the NR-PSS, NR-SSS, and NR-PBCH in a hybrid pattern oftime-domain and frequency-domain multiplexing. 1809 and 1810 areexamples of combination of repetition of NR-PSS, interleaving of NR-SSSand NR-PBCH in frequency domain, and hybrid multiplexing method, whererepetition of NR-PSS is performed in time domain and frequency domaincorrespondingly. 1811 is an example of repetition of NR-PSS in frequencydomain, but using shorter NR-PSS sequences. 1812 is an example ofrepetition of NR-PSS in both time and frequency domain, and usingdifferent numerologies.

As shown in FIG. 18C, 1813 is an example of multiplexing NR-PSS withNR-SSS and NR-PBCH, and with gap between the signals in time domain.1814 is an example of different multiplexing and mapping across SSblocks.

As shown in FIG. 19A, 1915, 1916, 1918, and 1919 are examples ofmultiplexing NR-PSS with NR-SSS and NR-PBCH, and with gap between thesignals in time domain where NR-SSS and NR-PBCH are positioned adjacentto each other. 1917 and 1920 are examples of multiplexing NR-PSS withNR-SSS and NR-PBCH, and with gap between the signals in time domainwhere NR-SSS and NR-PBCH occupy two symbols and are multiplexed(interleaved) in frequency domain. In 1915, 1416, and 1917, NR-PSS andNR-SSS/NR-PBCH are associated with two separate SS blocks.

As shown in FIG. 19B, 1921 to 1928 show multiplexing of NR-PSS withjointly coded NR-SSS and NR-PBCH. 1921 is an example of multiplexing ofNR-PSS with jointly coded NR-SSS and NR-PBCH in time domain wheremultiple jointly coded NR-SSS and NR-PBCH symbols are located on bothsides of NR-PSS. 1922 is an example of multiplexing of NR-PSS with jointcoded NR-SSS and NR-PBCH in time domain where multiple jointly codedNR-SSS and NR-PBCH symbols are located on the same side of NR-PSS. 1923is an example of multiplexing of NR-PSS with joint coded NR-SSS andNR-PBCH in time domain where jointly coded NR-SSS and NR-PBCH symbolsare located not next to NR-PSS within a SS block. 1924 is an example ofmultiplexing of NR-PSS with joint coded NR-SSS and NR-PBCH in timedomain with repetition of NR-PSS. 1925 is an example of multiplexing ofNR-PSS with jointly coded NR-SSS and NR-PBCH in frequency domain. 1926is an example of NR-PSS transmitted in one SS block and jointly codedNR-SSS and NR-PBCH transmitted in another SS block.

As shown in FIG. 19C, 1927 is an example of multiplexing of NR-PSS withjoint coded NR-SSS and NR-PBCH using different subcarrier spacing. 1428is an example of multiplexing of NR-PSS with joint coded NR-SSS andNR-PBCH using different bandwidth.

As shown in FIG. 20, 2029 is an example of multiplexing of NR-PBCH withinterleaved NR-PSS and NR-SSS using comb structure. 2030 is an exampleof multiplexing of multiple repetitions of NR-PBCH with interleavedNR-PSS and NR-SSS using comb structure. 2031 is an example ofmultiplexing NR-PSS and NR-SSS using comb structure in different symbols(positions for signals are interleaved in different symbols). 2032 is anexample of multiplexing NR-PSS and NR-SSS using comb structure indifferent symbols (positions for signals are interleaved in differentsymbols), and further multiplexing NR-SSS with NR-PBCH using theremaining REs in the same symbol. 2033 is same multiplexing method as2032 but with multiple repetitions of PBCH.

Note that combinations of the mapping and multiplexing schemes in FIGS.18A-C, 19A-C, and 20 are also supported in the present disclosure.

Each SS block periodicity can be of any time unit duration. Examples ofsuch a duration is half of a radio frame (such as 5 ms), one radio frame(such as 10 ms), or a multiple of radio frames (such as 10N-ms where Nis an integer greater than 1). An example embodiment is when one SSblock periodicity is 5 ms. For 1916, each of the NR-PSS and NR-SSS has asame periodicity of 10 ms and can be positioned at the last symbol (forinstance, of the last slot) within a 5 ms time duration. In this case,NR-PSS and NR-SSS can be detected without the knowledge of CP lengthregardless whether NR-PSS, NR-SSS, and NR-PBCH can be transmitted withdifferent CP lengths or not. If such is the case, CP length can bedetected as a part of NR-PBCH detection. For 1915, each of the NR-PSSand NR-SSS has a same periodicity of 10 ms. NR-PSS can be positioned atthe last symbol (for instance, of the last slot) within a 5 ms timeduration. NR-SSS, on the other hand, cannot. In this case, NR-PSS can bedetected without the knowledge of CP length regardless whether NR-PSS,NR-SSS, and NR-PBCH can be transmitted with different CP lengths or not.If such is the case, CP length can be detected as a part of NR-SSSdetection.

In some embodiments of component VI, except for indicating part of theNR cell ID, the NR-PSS sequence(s) can also be utilized to indicateother parameters.

In one embodiment, the NR-PSS sequence(s) can be utilized to indicatethe CP length/type of NR-SS. For example, one NR-PSS sequence isutilized for indicating that NR-SS is using the normal CP length,another NR-PSS sequence is utilized for indicating that NR-SS is usingthe extended CP length (if extended CP is support for NR-SS). In asub-embodiment, if the NR-PSS is using ZC-sequence, one ZC-sequence withroot k is utilized to indicate that NR-SS is using the normal CP length,another ZC-sequence with root l−k is utilized to indicate that NR-SS isusing the extended CP length (if extended CP is support for NR-SS),where l is the length of ZC-sequence (also means that the twoZC-sequences are conjugated).

In another embodiment, the NR-PSS sequence(s) can be utilized forindicating the CP length/type of data multiplexed with NR-SS. Forexample, one NR-PSS sequence is utilized to indicate that multiplexeddata are using the normal CP length, another NR-PSS sequence is utilizedto indicate that multiplexed data are using the extended CP length (ifextended CP is support for NR-SS). In a sub-embodiment, if the NR-PSS isusing ZC-sequence, one ZC-sequence with root k is utilized to indicatethat multiplexed data are using the normal CP length, anotherZC-sequence with root l−k is utilized to indicate that multiplexed dataare using the extended CP length (if extended CP is support for NR-SS),where l is the length of ZC-sequence (also means that the twoZC-sequences are conjugated).

In yet another embodiment, the NR-PSS sequence(s) can be utilized toindicate the combination of CP length/type and subcarrier spacing ofdata multiplexed with NR-SS. For example, each NR-PSS sequence isutilized to indicate one combination of CP length/type and subcarrierspacing of multiplexed data. In a sub-embodiment, if the NR-PSS is usingZC-sequence and there are two combinations of CP length/type andsubcarrier spacing of multiplexed data to be indicated, one ZC-sequencewith root k can be utilized to indicate the first combination of CPlength/type and subcarrier spacing of multiplexed data, and anotherZC-sequence with root l−k can be utilized to indicate the secondcombination of CP length/type and subcarrier spacing of multiplexeddata, where l is the length of ZC-sequence (also means that the twoZC-sequences are conjugated). For example, the first combination can benormal CP with 15 kHz subcarrier spacing, or normal CP with 30 kHzsubcarrier spacing for <6 GHz carrier frequency, and normal CP with 60kHz subcarrier spacing, or normal CP with 120 kHz subcarrier spacingfor >6 GHz carrier frequency, and the second combination can be extendedCP with 60 kHz subcarrier spacing for <6 GHz carrier frequency andextended CP with 240 kHz subcarrier spacing for >6 GHz carrierfrequency.

Note that the indication of other parameters can be combined with theindication of part of the NR cell ID, and also combined with otherdesign aspects in the aforementioned embodiment of component I. Forexample, M·N sequences can be utilized to indicate the combinations ofpart of the NR cell ID (N hypotheses) and the CP length and/orsubcarrier spacing (M hypotheses). For instance, N=3 and M=2. In onesub-embodiment, if ZC-sequence is utilized for constructing NR-PSS,sequences indicating different CP length and/or subcarrier spacing withthe same NR cell ID indication can be conjugated ZC-sequences.

Note that if there are multiple combinations of the part of the NR cellID, and/or CP length, and/or subcarrier spacing to be indicated, theNR-PSS sequence(s) can be utilized to indicate part of the combinations,and other signal(s) and/or channel(s) can be utilized to indicate theremaining combinations. Note that the above mentioned root pair ofZC-sequences (e.g. k and l−k) can be chosen based on the correlationproperty. For example, if l=63, then the root pair can be (29, 34) or(34, 29). For another example, if =127, then the root pair can be (29,98) or (98, 29). For yet another example, if 1=255, then the root paircan be (29, 226) or (226, 29).

The present disclosure focuses on the design of NR synchronizationsignals, termed the NR-SS including NR-PSS and NR-SSS. Some of theembodiments are also related to NR broadcast signals and channels,termed the NR-PBCH. The present disclosure relates generally to wirelesscommunication systems and, more specifically, to the sequence design ofNR synchronization signals, along with their associated mapping andprocedures. NR synchronization signals, termed the NR-SS, includeNR-PSS, NR-SSS and other potentially additional synchronization signalsin the present disclosure.

In some embodiments of component VII, the functionality of PSS is toprovide coarse time domain and frequency domain synchronization, as wellas part of the physical cell ID detection. The PSS is constructed from afrequency-domain Zadoff-Chu (ZC) sequence of length 63, with the middleelement truncated to avoid using the d.c. subcarrier. 3 roots areselected for PSS to represent the 3 physical layer identities withineach group of cells. The PSS is transmitted in the central 6 resourceblocks (RBs), invariant to the system bandwidth to enable the UE tosynchronize without a priori information of the system bandwidth.

For NR, one of the basic functionalities of NR-PSS is still to providecoarse time domain and frequency domain synchronization, and thefrequency location of NR-PSS can still be independent from the systembandwidth. However, other functionalities and designs of the NR-PSSsequence can be different from LTE specification, due to potentiallylarger synchronization transmission bandwidth (such that longer sequencelength), larger cell ID number, and larger periodicity.

Note that in one embodiment, NR-PSS is utilized only forfrequency-domain offset and timing detection, and possibly for part ofthe cell ID information, but not for carrying other hypotheses like SSblock timing index and CP type.

The following sub-components are distinguished based on differentmaximum number of resource elements available within one OFDM symbol fortransmitting NR-PSS.

In some embodiments of component VII.A, the maximum number of resourceelements available within one OFDM symbol for transmitting NR-PSS is 288(equivalent to 24 RBs), which corresponds to (note that the bandwidthcontains guard band, and actual transmission bandwidth can be a littlebit smaller): frequency range A associated with 15 kHz subcarrierspacing and 5 MHz NR-PSS transmission bandwidth (including guard band);frequency range B associated with 30 kHz subcarrier spacing and 10 MHzNR-PSS transmission bandwidth (including guard band); frequency range Cassociated with 60 kHz subcarrier spacing and 20 MHz NR-PSS transmissionbandwidth (including guard band); frequency range D associated with 120kHz subcarrier spacing and 40 MHz NR-PSS transmission bandwidth(including guard band); and frequency range E associated with 240 kHzsubcarrier spacing and 80 MHz NR-PSS transmission bandwidth (includingguard band).

In one example, frequency range A can be around 0 to 2 GHz, frequencyrange B can be around 2 to 6 GHz, frequency range D can be above 6 GHz.For another example, frequency range A can be around 0 to 2 GHz,frequency range B can be around 2 to 6 GHz, frequency range E can beabove 6 GHz. For yet another example, frequency range A can be around 0to 6 GHz, frequency range D can be above 6 GHz. For yet another example,frequency range A can be around 0 to 6 GHz, frequency range E can beabove 6 GHz.

In one embodiment, the same NR-PSS sequence(s) is utilized for thefrequency ranges A to E by scaling the subcarrier spacing.

Note that the numerology of NR-PSS can be different from datamultiplexed in the same symbol, so guard band is needed on both side ofNR-PSS sequence in frequency domain, and the size of guard band isaround 10% (which correspond to around 28 REs in this sub-embodiment)such that the maximum number of REs for transmitting NR-PSS may bereduced to around 260. Based on this consideration, the design of NR-PSSsequence can be selected as one of the following options.

In one embodiment of option 1, long ZC-sequence without multiplexing orinterleaved with other sequences (including zero sequence), the sequenced_(PSS)(n) used for NR-PSS is generated from a frequency-domainZC-sequence according to

${d_{PSS}(n)} = \{ \begin{matrix}{e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{PSS}}},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{e^{{- j}\frac{\pi \; {u{({n + 1})}}{({n + 2})}}{L_{PSS}}},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(PSS) is the length of NR-PSS sequence, and L_(PSS) is an oddnumber smaller than 260. In one example, L_(PSS)=255. In anotherexample, L_(PSS)=257. In yet another example, L_(PSS)=259.

FIG. 21 illustrates an example capability to resist CFO 2100 accordingto embodiments of the present disclosure. The embodiment of thecapability to resist CFO 2100 illustrated in FIG. 21 is for illustrationonly. FIG. 21 does not limit the scope of this disclosure to anyparticular implementation of the capability to resist CFO 2100.

The number of supported ZC-sequence root index u is given by the numberof cell ID hypotheses contained in NR-PSS, and a value of the number ofsupported ZC-sequence root index u can be chosen from capability of thenumber of supported ZC-sequence root index u to resist the frequencydomain offset (e.g. 5 ppm) and/or PAPR and/or CM properties. FIG. 21shows the capability to resist CFO corresponds to different roots.

FIG. 22 illustrates an example PAPR 2200 according to embodiments of thepresent disclosure. The embodiment of the PAPR 2200 illustrated in FIG.22 is for illustration only. FIG. 22 does not limit the scope of thisdisclosure to any particular implementation of the PAPR 2200.

FIG. 23 illustrates an example RCM value 2300 according to embodimentsof the present disclosure. The embodiment of the RCM value 2300illustrated in FIG. 23 is for illustration only. FIG. 23 does not limitthe scope of this disclosure to any particular implementation of the RCMvalue 2300.

FIG. 22 shows the PAPR value corresponds to different roots. FIG. 23shows the RCM value corresponds to different roots. Then taking into theconsideration of three aspect, the potential values for u forL_(PSS)=255 can be chosen from S₂₅₅={64, 107, 108, 110, 111, . . . ,118, 121, . . . , 126, 129, 130, . . . , 134, 137, . . . , 145, 147,148, 191}

In one example, if only one NR-PSS sequence is supported in NR (whichmeans no cell ID hypothesis in NR-PSS), there is one value for u(equivalent to defining a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0,where physical-layer cell-identity N_(ID)=N_(ID) ⁽¹⁾·N_(PSS)+N_(ID) ⁽²⁾and N_(PSS) is the number of NR-PSS sequences), and the correspondingvalue can be 125 (best capability against CFO) or the correspondingvalue's conjugate 130 (same capability against CFO as 125), or chosenfrom other values in S₂₅₅ In another example, the corresponding valuecan be 126 or the corresponding value's conjugate 129. In yet anotherexample, the corresponding value can be 121 or the corresponding value'sconjugate 134. In yet another example, the corresponding value can be116 or the corresponding value's conjugate 139. In yet another example,the corresponding value can be 64 or the corresponding value's conjugate191.

In another example, if two NR-PSS sequences are supported in NR torepresent two cell ID hypotheses, there are two possible values for u(each of them is mapped to a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0or 1), and the two values are conjugate roots for ZC-sequence (i.e., thesummation of values of u corresponding to N_(ID) ⁽²⁾=0 and 1correspondingly equals to the length of ZC-sequence). One of suchexample of u values for L_(PSS)=255 can be (125, 130) (best pair withcapability against CFO), or other conjugate pair chosen from S₂₅₅.Another example is (116, 139). Yet another example is (64, 191). Yetanother example is (121, 134). Yet another example is (126, 129).

In yet another example, if three NR-PSS sequences are supported in NR torepresent three cell ID hypotheses, there are three possible values foru (each of them is mapped to a cell ID component in NR-PSS as N_(ID)⁽²⁾=0 or 1 or 2), and two of the values are conjugate roots forZC-sequence (i.e., the summation of two values of u equals to the lengthof ZC-sequence), and the remaining one is chosen to have the best crosscorrelation with the conjugate pair (also selected from the set of bestcapability against CFO). One of such example of u values for L_(PSS)=255can be (125, 130, a) (best pair with capability against CFO and anotherone a chosen from set S₂₅₅ like a=121 or 134 or 126 or 129 or 116 or 139or 64 or 191), or other conjugate pair together with another root valuechosen from S₂₅₅. For another example, root set can be (121, 134, a),where a=125 or 130 or 126 or 129 or 116 or 139 or 64 or 191. For yetanother example, root set can be (126, 129, a), where a=125 or 130 or121 or 134 or 116 or 139 or 64 or 191. For yet another example, root setcan be (116, 139, a), where a=125 or 130 or 121 or 134 or 126 or 129 or64 or 191. For yet another example, root set can be (64, 191, a), wherea=125 or 130 or 121 or 134 or 116 or 139 or 116 or 139.

The sequence d_(PSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \;,{L_{PSS} - 2},{k = {{n - \frac{L_{PSS} - 1}{2} + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- \frac{288 - L_{PSS} + 1}{2}}},\ldots \;,{- 1},{L_{PSS} - 1},\ldots \;,{\frac{288 + L_{PSS} + 1}{2} - 2},{k = {n - \frac{L_{PSS} - 1}{2} + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-PSS is transmitted.

In one embodiment of option 2, short ZC-sequence interleaved with zerosequence, the sequence d_(PSS)(n) used for NR-PSS is generated from afrequency-domain ZC-sequence according to

${d_{PSS}(n)} = \{ \begin{matrix}{{\sqrt{2}*e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{PSS}}}},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{{\sqrt{2}*e^{{- j}\frac{\pi \; {u{({n + 1})}}{({n + 2})}}{L_{PSS}}}},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(PSS) is the length of NR-PSS sequence, and L_(PSS) is an oddnumber smaller than 130. In one example, L_(PSS)=127. In anotherexample, L_(PSS)=129.

FIG. 24 illustrates another example capability to resist CFO 2400according to embodiments of the present disclosure. The embodiment ofthe capability to resist CFO 2400 illustrated in FIG. 24 is forillustration only. FIG. 24 does not limit the scope of this disclosureto any particular implementation of the capability to resist CFO 2400.

The number of supported ZC-sequence root index u is given by the numberof cell ID hypotheses contained in NR-PSS, and a value of the number ofsupported ZC-sequence root index u can be chosen from capability of thenumber of supported ZC-sequence root index u to resist the frequencydomain offset (e.g. 5 ppm). For instance, as shown in FIG. 24, thepotential values for u for L_(PSS)=127 can be chosen from S₁₂₇={53, 54,. . . , 73, 74}.

In one example, if only one NR-PSS sequence is supported in NR (whichmeans no cell ID hypothesis in NR-PSS), there is one value for u(equivalent to defining a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0),and the corresponding value can be 62 (best capability against CFO) orcorresponding value's conjugate 65 (same capability against CFO as 62),or can be 61 (similar capability against CFO to 62) or correspondingvalue's conjugate 66 (same capability against CFO as 61), or chosen fromother values in S₁₂₇.

In another example, if two NR-PSS sequences are supported in NR torepresent two cell ID hypotheses, there are two possible values for u(each of them is mapped to a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0or 1), and the two values are conjugate roots for ZC-sequence (i.e., thesummation of values of u corresponding to N_(ID) ⁽²⁾=0 and 1correspondingly equals to the length of ZC-sequence). One of suchexample of u values for L_(PSS)=127 can be (62, 65) or (61, 66) (bestpairs with capability against CFO), or other conjugate pair chosen fromS₁₂₇.

In yet another example, if three NR-PSS sequences are supported in NR torepresent three cell ID hypotheses, there are three possible values foru (each of them is mapped to a cell ID component in NR-PSS as N_(ID)⁽²⁾=0 or 1 or 2), and two of the values are conjugate roots forZC-sequence (i.e., the summation of two values of u equals to the lengthof ZC-sequence), and the remaining one is chosen to have the best crosscorrelation with the conjugate pair (also selected from the set of bestcapability against CFO). One of such example of u values for L_(PSS)=127can be (62, 65, a) or (61, 66, a) (best pairs with capability againstCFO and another one a chosen from set S₁₂₇ like a=59 or 68), or otherconjugate pair together with another root value chosen from S₁₂₇.

The sequence d_(PSS)(n) is mapped to the resource elements according to

$a_{k,l} = \{ \begin{matrix}{{d(n)},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2},{k = {{2*n} - L_{PSS} + 1 + \frac{N_{RB}N_{SC}}{2}}}} \\{{d(n)},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2},{k = {{2*n} - L_{PSS} + 2 + \frac{N_{RB}N_{SC}}{2}}}}\end{matrix} $

and a_(k,l)=0 for the remaining k within the 288 REs with the samesymbol index l, where N_(RB) is number of total RBs for transmission,and N_(SC) is the number of subcarriers within a RB (e.g. N_(SC)=12). lcorresponds to the OFDM symbol index where NR-PSS is transmitted.

In one embodiment of option 3, long M-sequence without multiplexing orinterleaved with other sequences (including zero sequence), the sequenced_(PSS)(n) used for NR-PSS is generated from a frequency-domainM-sequence d_(M)(m) with length 255 (0≤m≤254) according to

${d_{PSS}(n)} = \{ \begin{matrix}{{1 - {2*{d_{M}(n)}}},{n = 0},1,\ldots \;,126} \\{{1 - {2*{d_{M}( {n + 1} )}}},{n = 127},\ldots \;,253}\end{matrix} $

where each of the d_(M)(m) is constructed based on TABLE 3, which showsthe recursive construction method and corresponding polynomial and tapsof register for M-sequence with power 8 (e.g. length 255).

TABLE 3 Recursive construction method Corresponding Corresponding No.Recursive construction method polynomial taps of register  1 d_(M)(i +8) = [d_(M)(i + 7) + x⁸ + x⁷ + x⁶+ [1, 2, 7, 8] d_(M)(i + 6) +d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  2 d_(M)(i + 8) =[d_(M)(i + 7) + x⁸ + x⁷ + x² + [1, 6, 7, 8] d_(M)(i + 2) +d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  3 d_(M)(i + 8) =[d_(M)(i + 7) + x⁸ + x⁷ + x⁵ + [1, 3, 5, 8] d_(M)(i + 5) + d_(M)(i +3) + x³ + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  4 d_(M)(i + 8) = [d_(M)(i +5) + x⁸ + x⁵ + x³ + [3, 5, 7, 8] d_(M)(i + 3) + d_(M)(i + 1) + x + 1d_(M)(i)]mod 2, 0 ≤ i ≤ 246  5 d_(M)(i + 8) = [d_(M)(i + 6) + x⁸ + x⁶ +x⁵ + [2, 3, 4, 8] d_(M)(i + 5) + d_(M)(i + 4) + x⁴ + 1 d_(M)(i)]mod 2, 0≤ i ≤ 246  6 d_(M)(i + 8) = [d_(M)(i + 4) + x⁸ + x⁴ + x³ + [4, 5, 6, 8]d_(M)(i + 3) + d_(M)(i + 2) + x² + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  7d_(M)(i + 8) = [d_(M)(i + 6) + x⁸ + x⁶ + x⁵ + [2, 3, 5, 8] d_(M)(i +5) + d_(M)(i + 3) + x³ + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  8 d_(M)(i + 8) =[d_(M)(i + 5) + x⁸ + x⁵ + x³ + [3, 5, 6, 8] d_(M)(i + 3) + d_(M)(i +2) + x² + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246  9 d_(M)(i + 8) = [d_(M)(i +6) + x⁸ + x⁶ + x⁵ + [2, 3, 6, 8] d_(M)(i + 5) + d_(M)(i + 2) + x² + 1d_(M)(i)]mod 2, 0 ≤ i ≤ 246 10 d_(M)(i + 8) = [d_(M)(i + 6) + x⁸ + x⁶ +x³ + [2, 5, 6, 8] d_(M)(i + 3) + d_(M)(i + 2) + x² + 1 d_(M)(i)]mod 2, 0≤ i ≤ 246 11 d_(M)(i + 8) = [d_(M)(i + 6) + x⁸ + x⁶ + x⁵ + [2, 3, 7, 8]d_(M)(i + 5) + d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246 12d_(M)(i + 8) = [d_(M)(i + 7) + x⁸ + x⁷ + x³ + [1, 5, 6, 8] d_(M)(i +3) + d_(M)(i + 2) + x² + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246 13 d_(M)(i + 8) =[d_(M)(i + 7) + x⁸ + x⁷ + x⁶ + [1, 2, 3, 4, d_(M)(i + 6) + d_(M)(i +5) + x⁵ + x⁴ + 6, 8] d_(M)(i + 4) + d_(M)(i + 2) + x² + 1 d_(M)(i)]mod2, 0 ≤ i ≤ 246 14 d_(M)(i + 8) = [d_(M)(i + 6) + x⁸ + x⁶ + x⁴ + [2, 4,5, 6, d_(M)(i + 4) + d_(M)(i + 3) + x³ + x² + 7, 8] d_(M)(i + 2) +d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246 15 d_(M)(i + 8) =[d_(M)(i + 7) + x⁸ + x⁷ + x⁶ + [1, 2, 3, 6, d_(M)(i + 6) + d_(M)(i +5) + x⁵ + x² + 7, 8] d_(M)(i + 2) + d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2,0 ≤ i ≤ 246 16 d_(M)(i + 8) = [d_(M)(i + 7) + x⁸ + x⁷ + x⁶ + [1, 2, 5,6, d_(M)(i + 6) + d_(M)(i + 3) + x³ + x² + 7, 8] d_(M)(i + 2) +d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 246

The initial condition can bed_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(S)=d_(M)(6)=0,d_(M)(7)=1, or can bed_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=d_(M)(6)=d_(M)(7)=1.

FIG. 25 illustrates yet another example capability to resist CFO 2500according to embodiments of the present disclosure. The embodiment ofthe capability to resist CFO 2500 illustrated in FIG. 25 is forillustration only. FIG. 25 does not limit the scope of this disclosureto any particular implementation of the capability to resist CFO 2500.

If only one NR-PSS sequence is supported in NR (which means no cell IDhypothesis in NR-PSS), there is one sequence from TABLE 3 utilized(equivalent to defining a cell ID component in NR-PSS as N=0), and theparticular sequence number can be one from TABLE 3 since all sequencesin TABLE 3 have similar capability for resisting CFO as shown in FIG.25.

If more than one NR-PSS sequences are supported in NR to represent thesame number of cell ID hypotheses (one sequence corresponds to one valueof N_(ID) ⁽²⁾, in one embodiment, these sequences are selected fromTABLE 3 such that the cross-correlation among the sequences ismaximized. In another embodiment, one sequence from TABLE 3 is utilizedas the base sequence, and cyclic shift and/or scrambling sequence isperformed on the base sequence to distinguish cell ID hypotheses.

The sequence d_(PSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \;,253,{k = {{n - 127 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 17}},\ldots \;,{- 1},254,\ldots \;,270,{k = {n - 127 + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-PSS is transmitted

In one embodiment of option 4, short M-sequence interleaved with zerosequence, the sequence d_(PSS)(n) used for NR-PSS is generated from aBPSK modulated frequency-domain M-sequence d(m) with length 127 as inoption 3 of Component I.B, but mapped to central and interleavedsubcarriers within the 288 subcarriers. For example, the length-127NR-PSS sequence is mapped to even subcarrier #14, #16, . . . , #266(subcarrier starting with #0). In one example, the length-127 NR-PSSsequence is mapped to even subcarrier #12, #14, . . . , #264 (subcarrierstarting with #0). In another example, the length-127 NR-PSS sequence ismapped to odd subcarrier #13, #15, . . . , #265 (subcarrier startingwith #0). For yet another example, the length-127 NR-PSS sequence ismapped to odd subcarrier #11, #13, . . . , #263 (subcarrier startingwith #0).

In some embodiments of component VII.B, the maximum number of resourceelements available within one OFDM symbol for transmitting NR-PSS is 144(equivalent to 12 RBs), which corresponds to (note that the bandwidthcontains guard band, and actual transmission bandwidth can be a littlebit smaller): frequency range A associated with 15 kHz subcarrierspacing and 2.5 MHz NR-PSS transmission bandwidth (including guardband); frequency range B associated with 30 kHz subcarrier spacing and 5MHz NR-PSS transmission bandwidth (including guard band); frequencyrange C associated with 60 kHz subcarrier spacing and 10 MHz NR-PSStransmission bandwidth (including guard band); frequency range Dassociated with 120 kHz subcarrier spacing and 20 MHz NR-PSStransmission bandwidth (including guard band); and frequency range Eassociated with 240 kHz subcarrier spacing and 40 MHz NR-PSStransmission bandwidth (including guard band).

In one example, frequency range A can be around 0 to 2 GHz, frequencyrange B can be around 2 to 6 GHz, frequency range D can be above 6 GHz.For another example, frequency range A can be around 0 to 2 GHz,frequency range B can be around 2 to 6 GHz, frequency range E can beabove 6 GHz. For yet another example, frequency range A can be around 0to 6 GHz, frequency range D can be above 6 GHz. For yet another example,frequency range A can be around 0 to 6 GHz, frequency range E can beabove 6 GHz.

In one embodiment, the same NR-PSS sequence(s) is utilized for thefrequency ranges A to E by scaling the subcarrier spacing.

Note that the numerology of NR-PSS can be different from datamultiplexed in the same symbol, so guard band is needed on both side ofNR-PSS sequence in frequency domain, and the size of guard band isaround 10% (which correspond to around 14 REs in this sub-embodiment)such that the maximum number of REs for transmitting NR-PSS may bereduced to around 130. Based on this consideration, the design of NR-PSSsequence can be selected as one of the following options.

In one embodiment of option 1, long ZC-sequence without multiplexing orinterleaved with other sequences (including zero sequence, the sequenced_(PSS)(n) used for NR-PSS is generated from a frequency-domainZC-sequence according to

${d_{PSS}(n)} = \{ \begin{matrix}{e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{PSS}}},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{e^{{- j}\frac{\pi \; {u{({n + 1})}}{({n + 2})}}{L_{PSS}}},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(PSS) is the length of NR-PSS sequence, and L is an odd numbersmaller than 130. In one example, L_(PSS)=127. In another example,L_(PSS)=129.

The number of supported ZC-sequence root index u is given by the numberof cell ID hypotheses contained in NR-PSS, and a value of the number ofsupported ZC-sequence root index u can be chosen from capability of thenumber of supported ZC-sequence root index u to resist the frequencydomain offset (e.g. 5 ppm) and/or PAPR and/or CM properties. Forinstance, as shown in FIG. 24, the potential values for u forL_(PSS)=127 can be chosen from S₁₂₇={53, 54, . . . , 73, 74}.

In one example, if only one NR-PSS sequence is supported in NR (whichmeans no cell ID hypothesis in NR-PSS), there is one value for u(equivalent to defining a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0),and the corresponding value can be 62 (best capability against CFO) orcorresponding value's conjugate 65 (same capability against CFO as 62),or can be 61 (similar capability against CFO to 62) or correspondingvalue's conjugate 66 (same capability against CFO as 61), or chosen fromother values in S₁₂₇.

In another example, if two NR-PSS sequences are supported in NR torepresent two cell ID hypotheses, there are two possible values for u(each of them is mapped to a cell ID component in NR-PSS as N_(ID)=0 or1), and the two values are conjugate roots for ZC-sequence (i.e., thesummation of values of u corresponding to N_(ID) ⁽²⁾=0 and 1correspondingly equals to the length of ZC-sequence). One of suchexample of u values for L_(PSS)=127 can be (62, 65) or (61, 66) (bestpairs with capability against CFO), or other conjugate pair chosen fromS₁₂₇.

In yet another example, if three NR-PSS sequences are supported in NR torepresent three cell ID hypotheses, there are three possible values foru (each of them is mapped to a cell ID component in NR-PSS as N_(ID)⁽²⁾=0 or 1 or 2), and two of the values are conjugate roots forZC-sequence (i.e., the summation of two values of u equals to the lengthof ZC-sequence), and the remaining one is chosen to have the best crosscorrelation with the conjugate pair (also selected from the set of bestcapability against CFO). One of such example of u values for L_(PSS)=127can be (62, 65, a) or (61, 66, a) (best pairs with capability againstCFO and another one a chosen from set S₁₂₇ like a=59 or 68), or otherconjugate pair together with another root value chosen from S₁₂₇.

The sequence d_(PSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \;,{L_{PSS} - 2},{k = {{n - \frac{L_{PSS} - 1}{2} + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- \frac{144 - L_{PSS} + 1}{2}}},\ldots \;,{- 1},{L_{PSS} - 1},\ldots \;,{\frac{144 + L_{PSS} + 1}{2} - 2},{k = {n - \frac{L_{PSS} - 1}{2} + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a R (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-PSS is transmitted.

In one embodiment of option 2, short ZC-sequence interleaved with zerosequence, the sequence d_(PSS)(n) used for NR-PSS is generated from afrequency-domain ZC-sequence according to

${d_{PSS}(n)} = \{ \begin{matrix}{{\sqrt{2}*e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{PSS}}}},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{{\sqrt{2}*e^{{- j}\frac{\pi \; {u{({n + 1})}}{({n + 2})}}{L_{PSS}}}},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(PSS) is the length of NR-PSS sequence, and L_(PSS) is an oddnumber smaller than 65. For example, L_(PSS)=63. For another example,L_(PSS)=65.

FIG. 26 illustrates yet another example capability to resist CFO 2600according to embodiments of the present disclosure. The embodiment ofthe capability to resist CFO 2600 illustrated in FIG. 26 is forillustration only. FIG. 26 does not limit the scope of this disclosureto any particular implementation of the capability to resist CFO 2600.

The number of supported ZC-sequence root index u is given by the numberof cell ID hypotheses contained in NR-PSS, and a value of the number ofsupported ZC-sequence root index u can be chosen from capability of thenumber of supported ZC-sequence root index u to resist the frequencydomain offset (e.g. 5 ppm). For instance, as shown in FIG. 26, thepotential values for u for L_(PSS)=63 can be chosen from S₆₃={26, 27, .. . , 36, 37}.

In one example, if only one NR-PSS sequence is supported in NR (whichmeans no cell ID hypothesis in NR-PSS), there is one value for u(equivalent to defining a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0),and the corresponding value can be 29 (best capability against CFO) orcorresponding value's conjugate 34 (same capability against CFO as 34),or can be 30 (similar capability against CFO to 29) or correspondingvalue's conjugate 33 (same capability against CFO as 30), or chosen fromother values in S₆₃.

In another example, if two NR-PSS sequences are supported in NR torepresent two cell ID hypotheses, there are two possible values for u(each of them is mapped to a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0or 1), and the two values are conjugate roots for ZC-sequence (i.e., thesummation of values of u corresponding to N_(ID) ⁽²⁾=0 and 1correspondingly equals to the length of ZC-sequence). One of suchexample of u values for L_(PSS)=63 can be (29, 34) or (30, 33) (bestpairs with capability against CFO), or other conjugate pair chosen fromS₆₃.

In yet another example, if three NR-PSS sequences are supported in NR torepresent three cell ID hypotheses, there are three possible values foru (each of them is mapped to a cell ID component in NR-PSS as N_(ID)⁽²⁾=0 or 1 or 2), and two of the values are conjugate roots forZC-sequence (i.e., the summation of two values of u equals to the lengthof ZC-sequence), and the remaining one is chosen to have the best crosscorrelation with the conjugate pair (also selected from the set of bestcapability against CFO). One of such example of u values for L_(PSS)=63can be (29, 34, a) or (30, 33, a) (best pairs with capability againstCFO and another one a chosen from set S₁₂₇ like a=26 or 37), or otherconjugate pair together with another root value chosen from S₁₂₇.

The sequence d_(PSS)(n) is mapped to the resource elements according to

$a_{k,l} = \{ \begin{matrix}{{d(n)},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2},{k = {{2*n} - L_{PSS} + 1 + \frac{N_{RB}N_{SC}}{2}}}} \\{{d(n)},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2},{k = {{2*n} - L_{PSS} + 2 + \frac{N_{RB}N_{SC}}{2}}}}\end{matrix} $

and a_(k,l)=0 for the remaining k within the 144 REs with the samesymbol index l, where N_(RB) is number of total RBs for transmission,and N_(SC) is the number of subcarriers within a RB (e.g. N_(SC)=12). lcorresponds to the OFDM symbol index where NR-PSS is transmitted.

In one embodiment of option 3, long M-sequence without multiplexing orinterleaved with other sequences (including zero sequence), the sequenced_(PSS)(n) used for NR-PSS is generated from a BPSK modulatedfrequency-domain M-sequence d(m) with length 127 (0≤m≤126) according to

${d_{PSS}(n)} = \{ \begin{matrix}{{1 - {2*{d_{M}(n)}}},{n = 0},1,\ldots \;,62} \\{{1 - {2*{d_{M}( {n + 1} )}}},{n = 63},\ldots \;,125}\end{matrix} $

if the DC subcarrier is truncated, or according tod_(PSS)(n)=1−2*d_(M)(n), n=0, 1, . . . , 126 if the DC subcarrier is nottruncated, where each of the d_(M)(m) is constructed based on TABLE 4,which shows the recursive construction method and correspondingpolynomial and taps of register for M-sequence with power 7 (e.g. length127).

TABLE 4 Recursive construction method Recursive constructionCorresponding Corresponding No. method polynomial taps of register  1d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶ + 1 [1, 7,] d_(M)(i)]mod 2, 0 ≤ i≤ 119  2 d_(M)(i + 7) = [d_(M)(i + 1) + x⁷ + x + 1 [6, 7] d_(M)(i)]mod2, 0 ≤ i ≤ 119  3 d_(M)(i + 7) = [d_(M)(i + 4) + x⁷ + x⁴ + 1 [3, 7]d_(M)(i)]mod 2, 0 ≤ i ≤ 119  4 d_(M)(i + 7) = [d_(M)(i + 3) + x⁷ + x³ +1 [4, 7] d_(M)(i)]mod 2, 0 ≤ i ≤ 119  5 d_(M)(i + 7) = [d_(M)(i + 6) +x⁷ + x⁶ + x⁵ + [1, 2, 3, 7] d_(M)(i + 5) + d_(M)(i + 4) + x⁴ + 1d_(M)(i)]mod 2, 0 ≤ i ≤ 119  6 d_(M)(i + 7) = [d_(M)(i + 3) + x⁷ + x³ +x² + x + [4, 5, 6, 7] d_(M)(i + 2) + d_(M)(i + 1) + 1 d_(M)(i)]mod 2, 0≤ i ≤ 119  7 d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶ + x⁵ + [1, 2, 5, 7]d_(M)(i + 5) + d_(M)(i + 2) + x² + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 119  8d_(M)(i + 7) = [d_(M)(i + 5) + x⁷ + x⁵ + x² + x + 1 [2, 5, 6, 7]d_(M)(i + 2) + d_(M)(i + 1) + d_(M)(i)]mod 2, 0 ≤ i ≤ 119  9 d_(M)(i +7) = [d_(M)(i + 5) + x⁷ + x⁵ + x⁴ + x³ + 1 [2, 3, 4, 7] d_(M)(i + 4) +d_(M)(i + 3) + d_(M)(i)]mod 2, 0 ≤ i ≤ 119 10 d_(M)(i + 7) = [d_(M)(i +4) + x⁷ + x⁴ + x³ + [3, 4, 5, 7] d_(M)(i + 3) + d_(M)(i + 2) + x² + 1d_(M)(i)]mod 2, 0 ≤ i ≤ 119 11 d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶ +x⁴ + x² + 1 [1, 3, 5, 7] d_(M)(i + 4) + d_(M)(i + 2) + d_(M)(i)]mod 2, 0≤ i ≤ 119 12 d_(M)(i + 7) = [d_(M)(i + 5) + x⁷ + x⁵ + x³ + x + 1 [2, 4,6, 7] d_(M)(i + 3) + d_(M)(i + 1) + d_(M)(i)]mod 2, 0 ≤ i ≤ 119 13d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶+ x⁴ + [1, 3, 6, 7] d_(M)(i + 4) +d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 119 14 d_(M)(i + 7) =[d_(M)(i + 6) + x⁷ + x⁶ + x³ + x + [1, 4, 6, 7] d_(M)(i + 3) +d_(M)(i + 1) + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 119 15 d_(M)(i + 7) =[d_(M)(i + 5) + x⁷ + x⁵ + x⁴ + x³ + [2, 3, 4, 5, d_(M)(i + 4) +d_(M)(i + 3) + x² + x + 1 6, 7] d_(M)(i + 2) + d_(M)(i + 1) +d_(M)(i)]mod 2, 0 ≤ i ≤ 119 16 d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶ +x⁵ + x⁴ + [1, 2, 3, 4, d_(M)(i + 5) + d_(M)(i + 4) + x³+ x² + 1 5, 7]d_(M)(i + 3) + d_(M)(i + 2) + d_(M)(i)]mod 2, 0 ≤ i ≤ 119 17 d_(M)(i +7) = [d_(M)(i + 6) + x⁷ + x⁶ + x⁵ + x³ + [1, 2, 4, 5, d_(M)(i + 5) +d_(M)(i + 3) + x²+ x + 1 6, 7] d_(M)(i + 2) + d_(M)(i + 1) +d_(M)(i)]mod 2, 0 ≤ i ≤ 119 18 d_(M)(i + 7) = [d_(M)(i + 6) + x⁷ + x⁶ +x⁵ + x⁴ + [1, 2, 3, 5, d_(M)(i + 5) + d_(M)(i + 4) + x²+ x + 1 6, 7]d_(M)(i + 2) + d_(M)(i + 1) + d_(M)(i)]mod 2, 0 ≤ i ≤ 119

The initial condition can bed_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1, orcan be d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=d_(M)(6)=1,or other values that can facilitate small PAPR/CM value of the sequence.

FIG. 27 illustrates yet another example capability to resist CFO 2700according to embodiments of the present disclosure. The embodiment ofthe capability to resist CFO 2700 illustrated in FIG. 27 is forillustration only. FIG. 27 does not limit the scope of this disclosureto any particular implementation of the capability to resist CFO 2700.

If only one NR-PSS sequence is supported in NR (which means no cell IDhypothesis in NR-PSS), there is one sequence from TABLE 4 utilized(equivalent to defining a cell ID component in NR-PSS as N_(ID) ⁽²⁾=0),and the particular sequence number can be one from TABLE 4 since allsequences in TABLE 4 have similar capability for resisting CFO as shownin FIG. 27.

If more than one NR-PSS sequences are supported in NR to represent thesame number of cell ID hypotheses carried by NR-PSS (one NR-PSS sequencecorresponds to one value of N_(ID) ⁽²⁾ in one embodiment, thesesequences are selected from TABLE 4 such that the cross-correlationamong the sequences is maximized. In another embodiment, one sequencefrom TABLE 4 is utilized as the base sequence, and cyclic shift and/orscrambling sequence is performed on the base sequence to represent cellID hypotheses carried by NR-PSS.

The sequence d_(PSS)(n) is mapped to the central resource elementswithin the symbol for NR-PSS according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \;,125,{k = {{n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 9}},\ldots \;,{- 1},126,\ldots \;,134,{k = {n - 63 + \frac{N_{RB}N_{SC}}{2}}}$

if the DC subcarrier is truncated and according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \;,126,{k = {{n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 9}},\ldots \;,{- 1},127,\ldots \;,134,{k = {{n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {or}\mspace{14mu} a_{k,l}}} = {d_{PSS}( {n + 1} )}}},{n = {- 1}},\ldots \;,125,{k = {{n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 9}},\ldots \;,{- 2},126,\ldots \;,134,{k = {n - 63 + \frac{N_{RB}N_{SC}}{2}}}$

if the DC subcarrier is not truncated, where N_(RB) is number of totalRBs for NR-PSS transmission (e.g. N_(RB)=12), and N_(SC) is the numberof subcarriers within a RB (e.g. N_(SC)=12). l corresponds to the OFDMsymbol index where NR-PSS is transmitted.

In some embodiments of component VIII, the functionality of SSS sequenceis to detect the other part of cell ID based on the coarse time-domainand frequency-domain synchronization detection from PSS. CP size andduplexing mode information are also detected by SSS. The construction ofSSS sequences are based on the maximum length sequences (also known asM-sequences). Each SSS sequence is constructed by interleaving twolength-31 BPSK modulated subsequences in frequency domain, where the twosubsequences are constructed from the same M-sequence using differentcyclic shifts. The cyclic shift indices for both parts are functions ofthe physical cell ID group.

For NR, the basic functionalities of NR-SSS remain to detect the cell IDor part of the cell ID, CP size and duplexing mode if supported in NR,as well as other possible information carried by NR-SSS (e.g. SS blocktiming index). The functionalities and designs of the NR-SSS sequencecan be different from LTE system, due to potentially largersynchronization transmission bandwidth (such that longer sequencelength), larger cell ID number, and larger periodicity.

Note that in one embodiment, NR-SSS is mapped to the same number ofREs/subcarriers within one OFDM symbol as NR-PSS (repetition of NR-SSSand/or NR-PSS symbols in time domain is not counted), and the twosignals are multiplexed in time domain using the same numerology.

The following sub-components are distinguished based on differentmaximum number of resource elements available within one OFDM symbol fortransmitting NR-SSS.

In one embodiment of component VIII.A, design of One-port NR-SSSSequence for 288 REs, the maximum number of resource elements availablewithin one OFDM symbol for transmitting NR-SSS is 288 (equivalent to 24RBs), which corresponds to (note that the bandwidth contains guard band,and actual transmission bandwidth can be a little bit smaller):frequency range A associated with 15 kHz subcarrier spacing and 5 MHzNR-PSS transmission bandwidth (including guard band); frequency range Bassociated with 30 kHz subcarrier spacing and 10 MHz NR-PSS transmissionbandwidth (including guard band); frequency range C associated with 60kHz subcarrier spacing and 20 MHz NR-PSS transmission bandwidth(including guard band); frequency range D associated with 120 kHzsubcarrier spacing and 40 MHz NR-PSS transmission bandwidth (includingguard band); and frequency range E associated with 240 kHz subcarrierspacing and 80 MHz NR-PSS transmission bandwidth (including guard band).

In one example, frequency range A can be around 0 to 2 GHz, frequencyrange B can be around 2 to 6 GHz, frequency range D can be above 6 GHz.For another example, frequency range A can be around 0 to 2 GHz,frequency range B can be around 2 to 6 GHz, frequency range E can beabove 6 GHz. For yet another example, frequency range A can be around 0to 6 GHz, frequency range D can be above 6 GHz. For yet another example,frequency range A can be around 0 to 6 GHz, frequency range E can beabove 6 GHz.

In one embodiment, the same NR-SSS sequence(s) is utilized for thefrequency ranges A to E by scaling the subcarrier spacing.

Note that the numerology of NR-SSS can be different from datamultiplexed in the same symbol, so guard band is needed on both side ofNR-SSS sequence in frequency domain, and the size of guard band isaround 10% (which correspond to around 28 REs in this sub-embodiment)such that the maximum number of REs for transmitting NR-SSS may bereduced to around 260, and the same as NR-PSS. Based on thisconsideration, the design of one-port based NR-SSS sequence can beselected as one of the following options.

In one embodiment of option 1, interleaved two M-sequences, for thedesign of one-port based NR-SSS sequence for 288 REs using M-sequences,the NR-SSS sequence is with length 254, and the sequence d_(SSS)(0), . .. , d_(SSS)(253) is an interleaved concatenation of two length-127binary sequences, where each of the binary sequence is constructed basedon length-127 M-sequences. The concatenated sequence is scrambled with ascrambling sequence using the cell ID information in NR-PSS if there issuch information in NR-PSS, or scrambled by an all one sequence(equivalent as no scrambling) or a common scrambling sequence for allcell ID if there is no cell ID information in NR-PSS.

More precisely, the combination of two length-127 sequences defining theNR-SSS is according to d_(SSS)(2n)=s_(m) ₀ (n)c₀(n)z_(x)(n), andd_(SSS)(2n+1)=s_(m) ₁ (n)c₁(n)z_(y)(n) where 0≤n≤126, and the particularmeaning of parameters and sequences in the equations are detailed asfollow.

In one embodiment, NR-SSS only carries part of or the whole cell IDinformation and no timing information, or NR-SSS carries both part of orthe whole cell ID information and timing information, but timinginformation is carried by z_(x)(n), then the number of hypotheses to besupported by the combination of m₀ and m₁ is N_(SSS) (note thatN_(SSS)·N_(PSS) is the number of cell ID in this case). The combinationof m₀ and m₁ to represent a hypotheses H can be according to (equivalentto TABLE 5) m₀=m′ mod 127,

${m_{1} = {( {m_{0} + \lfloor \frac{m^{\prime}}{127} \rfloor + 1} )\mspace{14mu} {mod}\mspace{14mu} 127}},{m^{\prime} = {H + {{q( {q + 1} )}\text{/}2}}},{q = \lfloor \frac{H + {q\; {\prime ( {q^{\prime} + 1} )}\text{/}2}}{126} \rfloor},{{{and}\mspace{14mu} q^{\prime}} = \lfloor \frac{H}{126} \rfloor}$

and the N_(SSS) cell ID hypotheses can be selected from the 8001hypotheses. In one sub-embodiment, N_(ID) ⁽¹⁾ can be chosen as the firstN_(SSS) hypotheses in TABLE 5, i.e., H=N_(ID) ⁽¹⁾ for 0≤N_(ID)⁽¹⁾≤N_(SSS)−1. In another sub-embodiment, N_(ID) ⁽¹⁾ can be uniformedselected from the 8001 hypotheses in TABLE 5, e.g. H=a·N_(ID) ⁽¹⁾+b for0≤N_(ID) ⁽¹⁾≤N_(SSS)−1, and a can be 2 or 3 or . . . or └8001/N_(SSS)┘,and b can be 0 or 1 or . . . or a−1.

TABLE 5 Combination of m₀ and m₁ H m₀ m₁ H m₀ m₁ H m₀ m₁ H m₀ m₁  0  0 1 251  0  3 . . . . . . . . . . . . . . . . . .  1  1  2 252  1  4 . .. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .. . . . . . . 7995 0 124 125 125 126 374 123 126 . . . . . . . . . 79961 125 126  0  2 375  0  4 . . . . . . . . . 7997 2 126 127  1  3 376  1 5 . . . . . . . . . 7998 0 125 . . . . . . . . . . . . . . . . . . . .. . . . . . . 7999 1 126 250 124 126 497 122 126 . . . . . . . . . 80000 126

In another embodiment, NR-SSS carries both part of or the whole cell IDinformation and timing information, and the number of hypotheses to besupported by the combination of m₀ and m₁ is N_(SSS)·N_(b) (note thatN_(SSS)·N_(PSS) is the number of cell ID in this case), where N_(b) isthe number of timing information hypotheses to be carried by thecombination of m₀ and m₁. For example, in single beam system, if NR-SSScarries timing information indicating the NR-SSS symbol index whenmultiple NR-SSS are transmitted within a radio frame (e.g., similar toLTE specification), then N_(b) can be the number of possible positionsof NR-SSS within a radio frame. For another example, in multiple beamsystem, N_(b) can be the number of SS block timing index to be indicatedby current NR-SSS (note that it can be the whole SS block timing indexinformation or part of it). The combination of m₀ and m₁ to represent ahypotheses H can be the same as the previous embodiment (also equivalentto TABLE 5) and the N_(SSS)·N_(b) hypotheses can be selected from the8001 hypotheses in TABLE 5. In one sub-embodiment, the combination ofcell ID hypothesis N_(ID) ⁽¹⁾ and timing index l_(b) can be chosen asthe first N_(SSS)·N_(PSS) hypotheses in TABLE 5, e.g. H=N_(b)·N_(ID)⁽¹⁾+I_(b) for 0≤N_(ID) ⁽¹⁾≤N_(SSS)−1 and 0≤I_(b)≤N_(b)−1, orH=I_(b)·N_(SSS)+N_(ID) ⁽¹⁾ for 0≤N_(ID) ⁽¹⁾≤N_(SSS)−1 and0≤I_(b)≤N_(b-1).

The two sequences s_(m) ₀ (n) and s_(m) ₁ (n) are defined as twodifferent cyclic shifts of the M-sequence {tilde over (s)}(n) withlength 127 according to s_(m) ₀ (n)={tilde over (s)}((n+m₀) mod 127) ands_(m) ₁ (n)={tilde over (s)}((n+m₁) mod 127), and {tilde over (s)}(n)can be constructed based one of the M-sequence specified in TABLE 4according to {tilde over (s)}(n)=1−2*d_(M)(n) for 0≤n≤126 with a properinitial condition. For example, No. 3 in TABLE 4 is utilized, thend_(M)(i+7)=[d_(M)(i+4)+d_(M)(i)]mod 2, 0≤i≤119 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

In another example, No. 1 in TABLE 4 is utilized, thend_(M)(i+7)=[d_(M)(i+6)+d_(M)(i)]mod 2, 0≤i≤119 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

In one embodiment, the two scrambling sequences c₀(n) and c₁(n) dependon the cell ID information in NR-PSS (e.g. N_(ID) ⁽²⁾ and note that evenno cell ID information is carried by NR-PSS, the construction method inthis embodiment still work by considering N_(ID) ⁽²⁾=0) and are definedby different cyclic shifts of the M-sequence {tilde over (c)}(n) withlength 127 according to c₀(n)={tilde over (c)}((n+N_(ID) ⁽²⁾) mod 127)and c₁(n)={tilde over (c)}((n+N_(ID) ⁽²⁾+N_(PSS)) mod 127 where N_(PSS)is the number of NR-PSS sequences (or equivalent to the number ofhypotheses of cell ID carried by NR-PSS), and {tilde over (c)}(n) can beconstructed based one of the M-sequence specified in TABLE 4 (must bedifferent from the one generating {tilde over (s)}(n)) according to{tilde over (c)}(n)=1−2*d_(M)(n) for 0≤n≤126 with a proper initialcondition. For example, if No. 3 in TABLE 4 is utilized for generating{tilde over (s)}(n), then No. 4 can be utilized for generating {tildeover (c)}(n) as d_(M)(i+7)=[d_(M)(i+3)+d_(M)(i)]mod 2, 0≤i≤119 andd(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

In another example, No. 1 in TABLE 4 is utilized for generating {tildeover (s)}(n), then No. 2 can be utilized for generating {tilde over(c)}(n) as d_(M)(i+7)=[d(i+1)+d(i)]mod 2, 0≤i≤119 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

In another embodiment, if there is no cell ID information is carried byNR-PSS, the two scrambling sequences c₀(n) and c₁(n) can be independentfrom cell ID information in NR-PSS and constructed the same way usingM-sequence {tilde over (c)}(n) with length 127 according toc₀(n)=c₁(n)={tilde over (c)}(n) where {tilde over (c)}(n) can beconstructed based one of the M-sequence specified in TABLE 4 (must bedifferent from the one generating {tilde over (s)}(n)) according to{tilde over (c)}(n)=1−2*d_(M)(n) for 0≤n≤126 with a proper initialcondition. For example, if No. 3 in TABLE 4 is utilized for generating{tilde over (s)}(n), then No. 4 can be utilized for generating {tildeover (c)}(n) as d_(M)(i+7)=[d_(M)(i+3)+d_(M)(i)]mod 2, 0≤i≤119 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

For another example, No. 1 in TABLE 4 is utilized for generating {tildeover (s)}(n), then No. 2 can be utilized for generating {tilde over(c)}(n) as d_(M)(i+7)=[d(i+1)+d(i)]mod 2, 0≤i≤119 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0, d_(M)(6)=1.

In yet another embodiment, if there is no cell ID information is carriedby NR-PSS, the two scrambling sequences c₀(n) and c₁(n) can beindependent from cell ID information in NR-PSS and constructed the sameway according to c₀(n)=c₁(n)=1 which is equivalent to no scramblingsequence performed.

In one embodiment, the sequence z_(x)(n) and z_(y) (n) are based on thecell ID information in NR-PSS (in this case x=m₁ and y=m₀), and definedby a cyclic shift of the M-sequence {tilde over (z)}(n) with length-127according to z_(y)(n)=z_(m) ₀ (n)=2((n+(m₀ mod z)) mod 127) andz_(x)(n)=z_(m) ₁ (n)={tilde over (z)}((n+(m_(i) mod z)) mod 127) where zis a parameter related the total number of hypotheses carried bycombination of m₀ and m₁ (can refer to number of cell ID hypotheses orcombination of cell ID and timing information), and {tilde over (z)}(n)can be constructed based on one of the M-sequence specified in TABLE 4(must be different from the ones generating {tilde over (s)}(n) and{tilde over (c)}(n)) according to {tilde over (z)}(n)=1−2*d_(M)(n) for0≤n≤126 with a proper initial condition. For example, if No. 3 in TABLE4 is utilized for generating {tilde over (s)}(n), and No. 4 is utilizedfor generating {tilde over (c)}(n), then No. 18 can be utilized forgenerating {tilde over (z)}(n) with a proper initial conditiond_(M)(i+7)=[d(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+2)+d_(M)(i+1)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In another example, if No. 1 in TABLE 4 is utilized for generating{tilde over (s)}(n), and No. 2 is utilized for generating {tilde over(c)}(n), then No. 16 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+7)=[d(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In another embodiment, one of the sequence z_(x)(n) and z_(y)(n) arebased on the cell ID information in NR-PSS (in this case y=m₀), anddefined by a cyclic shift of the M-sequence {tilde over (z)}(n) withlength-127 according to z_(x)(n)=1 and z_(y) (n)=z_(m) ₀ (n)=2((n+(m₀mod z)) mod 127) where z is a parameter related the total number ofhypotheses carried by combination of m₀ and m₁ (can refer to number ofcell ID hypotheses or combination of cell ID and timing information),and {tilde over (z)}(n) can be constructed based on one of theM-sequence specified in TABLE 4 (must be different from the onesgenerating {tilde over (s)}(n) and {tilde over (c)}(n)) according to{tilde over (z)}(n)=1−2*d_(M)(n) for 0≤n≤126 with a proper initialcondition. For example, if No. 3 in TABLE 4 is utilized for generating{tilde over (s)}(n), and No. 4 is utilized for generating {tilde over(c)}(n), then No. 18 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+7)=[d_(M)(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+2)+d_(M)(i+1)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In another example, if No. 1 in TABLE 4 is utilized for generating{tilde over (s)}(n), and No. 2 is utilized for generating {tilde over(c)}(n), then No. 16 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+7)=[d(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In yet another embodiment, the sequence z_(x)(n) and z_(y)(n) are basedon the timing information, e.g. part of or the whole SS block timingindex I_(b) (in this case x=y=b), and defined by a cyclic shift of theM-sequence {tilde over (z)}(n) with length-127 according toz_(x)(n)=z_(y)(n)=z_(b)(n)={tilde over (z)}((n+b) mod 127) where {tildeover (z)}(n) can be constructed based on one of the M-sequence specifiedin TABLE 4 (must be different from the ones generating {tilde over(s)}(n) and {tilde over (c)}(n)) according to {tilde over(z)}(n)=1−2*d_(M)(n) for 0≤n≤126 with a proper initial condition. Forexample, if No. 3 in TABLE 4 is utilized for generating {tilde over(s)}(n), and No. 4 is utilized for generating {tilde over (c)}(n), thenNo. 18 can be utilized for generating {tilde over (z)}(n) with a properinitial conditiond_(M)(i+7)=[d_(M)(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+2)+d_(M)(i+1)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In another example, if No. 1 in TABLE 4 is utilized for generating{tilde over (s)}(n), and No. 2 is utilized for generating {tilde over(c)}(n), then No. 16 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+7)=[d(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In yet another embodiment, one of the sequence z_(x)(n) and z_(y)(n) arebased on the timing information, e.g. part of or the whole SS blocktiming index I_(b) (in this case e.g. y=b), and defined by a cyclicshift of the M-sequence {tilde over (z)}(n) with length-127 according toz_(x)(n)=1z_(y)(n)=z_(b)(n)={tilde over (z)}((n+b) mod 127) where {tildeover (z)}(n) can be constructed based one of the M-sequence specified inTABLE 4 (may be different from the ones generating {tilde over (s)}(n)and {tilde over (c)}(n)) according to {tilde over (z)}(n)=1−2*d_(M)(n)for 0≤n≤126 with a proper initial condition. For example, if No. 3 inTABLE 4 is utilized for generating {tilde over (s)}(n), and No. 4 isutilized for generating {tilde over (c)}(n), then No. 18 can be utilizedfor generating {tilde over (z)}(n) with a proper initial conditiond_(M)(i+7)=[d_(M)(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+2)+d_(M)(i+1)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In another example, if No. 1 in TABLE 4 is utilized for generating{tilde over (s)}(n), and No. 2 is utilized for generating {tilde over(c)}(n), then No. 16 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+7)=[d(i+6)+d_(M)(i+5)+d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod2, 0≤i≤119 and d_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=d_(M)(5)=0,d_(M)(6)=1.

In yet another embodiment, the sequence z_(x)(n) is not related to thecell ID information or timing information, and is defined by z_(x)(n)=1for 0≤n≤126 which is equivalent to no scrambling sequence performed. Thesequence d_(SSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \;,253,{k = {{n - 127 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 17}},\ldots \;,{- 1},254,\ldots \;,270,{k = {n - 127 + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-SSS is transmitted.

In one embodiment of option 2, ZC-sequences with cyclic shift, for thedesign of one-port based NR-SSS sequence for 288 REs using ZC-sequenceswith cyclic shifts, defining the NR-SSS is according to

${d_{SSS}(n)} = \{ \begin{matrix}{{d_{ZC}^{({u,v})}(n)},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{{d_{ZC}^{({u,v})}( {n + 1} )},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(SSS) is the length of NR-SSS sequence, and L_(SSS) is an oddnumber smaller than 260. For example, L_(SSS)=255. For another example,L_(SSS)=257. For yet another example, L_(SSS)=259. d_(ZC) ^((u,v))(n) isa length-L_(SSS) ZC-sequence with root index u∈U and cyclic shift valuev∈V, according to

${{d_{ZC}^{({u,v})}(n)} = {{{d_{ZC}^{(u)}( {( {n + v} ){mod}\; L_{SSS}} )}\mspace{14mu} {and}\mspace{14mu} d_{ZC}^{(u)}} = {{e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{SSS}}}\mspace{14mu} {for}\mspace{14mu} n} = 0}}},1,\ldots \;,{L_{SSS} - 1.}$

In one embodiment, if NR-SSS only carries part of or the whole cell IDhypotheses, then the combination of u and v may be large enough to coverthe number of cell ID hypotheses (e.g. N_(SSS)≤|U|·|V|, where |U| and|V| mean the size of sets U and V correspondingly). The mapping ofN_(ID) ⁽¹⁾ (0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) to u and v is according to

${u = {U( {\lfloor \frac{N_{ID}^{(1)}}{V} \rfloor + 1} )}},{v = {V( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {V}} ) + 1} )}},{{{or}\mspace{14mu} v} = {V( {\lfloor \frac{N_{ID}^{(1)}}{U} \rfloor + 1} )}},{u = {U( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {U}} ) + 1} )}}$

where the set can be a subset of {0, 1, . . . , 254} when L_(SSS)=255considering the sequences' maximum cross-correlation within the set, andset V can be a subset of {0, 1, . . . , 254}. For N_(SSS)=1000 (orapproximately 1000), the following combination of U and V in TABLE 6 canbe used for L_(SSS)=255.

TABLE 6 Combination of U and V U V |U| = 4, e.g. U = |V| = 255, e,g, V ={121, 125, 130, 134} {0, 1, . . . , 254} |U| = 8, e.g. U = {113, |V| =128, e.g. V = 117, 121, 125, 130, {0, 2, . . . , 254} or 134, 138, 142}{0, 1, . . . , 127}

In another embodiment, if NR-SSS carries part of or the whole cell IDhypotheses as well as timing information (e.g. SS block timing index orpart of the SS block timing index), then the combination of u and v maybe large enough to cover the number of cell ID hypotheses together withtiming hypotheses (e.g. N_(SSS)·N_(b)≤|U|·|V|, where |U| and |V| meanthe size of sets U and V correspondingly, and N_(b) is the number oftiming hypotheses carried by NR-SSS). The mapping of N_(ID) ⁽¹⁾(0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) and I_(b) (0≤I_(b)≤N_(b)−1) to u and v isaccording to u=U(└(N_(ID) ⁽¹⁾·N_(b)+I_(b))/|V|┘+1) and v=V(((N_(ID)⁽¹⁾·N_(b)+I_(b)) mod |V|)+1), or u=U(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|V|┘+1)and v=V(((N_(ID) ⁽¹⁾·N_(b)+I_(b)·N_(SSS)) mod |V|)+1), or v=V(└(N_(ID)⁽¹⁾·N_(b)+I_(b))/|U|┘+1) and u=U(((N_(ID) ⁽¹⁾·N_(b)+I_(b)) mod |U|)+1),or v=V(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|U|┘+1) and u=U(((N_(ID)⁽¹⁾+I_(b)·N_(SSS)) mod |U|)+1) where the set U can be a subset of {0, 1,. . . , 254} when L_(SSS)=255 considering the sequences' maximumcross-correlation within the set, and set V can be a subset of {0, 1, .. . , 254}. For N_(SSS)=1000 (or approximately 1000), and for differentvalue of N_(b), the following combination of U and V in TABLE 7 can beused for L_(SSS)=255.

TABLE 7 Combination of U and V N_(b) U V  2 |U| = 8, e.g. U = |V| = 255,e,g, V = {113, 117, 121, 125, {0, 1, . . . , 254} 130, 134, 138, 142}  2|U| = 16, e.g. U = {113, |V| = 128, e.g. V = 115, 117, 119, 121, 123,{0, 2, . . . , 254} or 125, 126, 129, 130, 132, {0, 1, . . . , 127} 134,136, 138, 140, 142}  4 |U| = 16, e.g. U = {111, |V| = 255, e,g, V = 113,115, 117, 119, 121, {0, 2, . . . , 254} 123, 125, 130, 132, 134, 136,138, 140, 142, 144}  4 |U| = 32, e.g. U = {95, |V| = 128, e.g. V = 97, .. . , 121, 123, 125, {0, 2, . . . , 254} or 130, 132, 134, . . . , 158,{0, 1, . . . , 127} 160}  8 |U| = 32, e.g. U = {95, |V| = 255, e,g, V =97, . . . , 121, 123, 125, {0, 1, . . . , 254} 130, 132, 134, . . . ,158, 160}  8 |U| = 64, e.g. U = {63, |V| = 128, e.g. V = 65, . . . ,121, 123, 125, {0, 2, . . . , 254} or 130, 132, 134, . . . , 190, {0, 1,. . . , 127} 192} 16 |U| = 64, e.g. U = {63, |V| = 255, e,g, V = 65, . .. , 121, 123, 125, {0, 1, . . . , 254} 130, 132, 134, . . . , 190, 192}16 |U| = 128, e.g. U = {63, |V| = 128, e.g. V = 64, 65, . . . , 124,125, {0, 2, . . . , 254} or 130, 131, . . . , 190, 191, {0, 1, . . . ,127} 192} 32 |U| = 128, e.g. U = {63, |V| = 255, e,g, V = 64, 65, . . ., 124, 125, {0, 1, . . . , 254} 130, 131, . . . , 190, 191, 192} 32 |U|= 255, e.g. U = {0, |V| = 128, e.g. V = 1, . . . , 254} {0, 2, . . . ,254} or {0, 1, . . . , 127} 64 |U| = 255, e.g. U = {0, |V| = 255, e,g, V= 1, . . . , 254} {0, 1, . . . , 254}

The sequence d_(SSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \;,{L_{SSS} - 2},{k = {{n - \frac{L_{SSS} - 1}{2} + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- \frac{288 - L_{SSS} + 1}{2}}},\ldots \;,{- 1},{L_{SSS} - 1},\ldots \;,{\frac{288 + L_{SSS} + 1}{2} - 2},{k = {n - \frac{L_{SSS} - 1}{2} + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-SSS is transmitted.

In one embodiment of option 3, length-255 M-sequences with cyclic shift,for the design of one-port based NR-SSS sequence for 288 REs usingM-sequences with cyclic shifts, defining the NR-SSS is according to

${d_{SSS}(n)} = \{ \begin{matrix}{{{2*{d_{M}^{({u,v})}(n)}} - 1},{n = 0},1,\ldots \;,126} \\{{{2*{d_{M}^{({u,v})}( {n + 1} )}} - 1},{n = 127},\ldots \;,253}\end{matrix} $

where d_(M) ^((u,v))(n) is a length-255 M-sequence with number index uand cyclic shift value v∈V, according to d_(M) ^((u,v))(n)=d_(M)^((u))((n+v)mod 255) and d_(M) ^((u)) is the No. u (1≤u≤16) sequencedefined in TABLE 3.

In one embodiment, if NR-SSS only carries part of or the whole cell IDhypotheses, then the combination of u and v may be large enough to coverthe number of cell ID hypotheses in NR-SSS (e.g. N_(SSS)≤|U|·|V|, where|U| and |V| mean the size of sets U and V correspondingly). The mappingof N_(ID) ⁽¹⁾ (0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) to u and v is according to

$u = {U( {\lfloor \frac{N_{ID}^{(1)}}{V} \rfloor + 1} )}$

and v=V((N_(ID) ⁽¹⁾ mod |V|)+1), or v=V(└N_(ID) ⁽¹⁾/|U|┘+1) andu=U((N_(ID) ⁽¹⁾ mod |U|)+1) where the set U can be a subset of {1, . . ., 16} considering the sequences' maximum cross-correlation within theset, and set V can be a subset of {0, 1, . . . , 254}. For N_(SSS)=1000(or approximately 1000), the following combination of U and V in TABLE 8can be used.

TABLE 8 Combination of U and V U V |U| = 4, e.g. U = {1, 2, 3, 4} |V| =255, e,g, V = {0, 1, . . . , 254} |U| = 8, e.g. U = {1, 2, 3, 4, |V| =128, e.g. V = 5, 6, 7, 8} {0, 2, . . . , 254} or {0, 1, . . . , 127} |U|= 16, e.g. U = {1, 2, 3, 4, |V| = 64, e.g. V = 5, 6, 7, 8, 9, 10, 11,12, 13, {0, 4, . . . , 252} or 14, 15, 16} {0, 1, . . . , 63}

For N_(SSS)=1000/N_(PSS) (or approximately 1000/N_(PSS), where N_(PSS)is the number of NR-PSS sequences), the following combination of U and Vin TABLE 9 can be used. In this case, a scrambling sequence can beapplied to represent the cell ID in NR-PSS, where the scramblingsequence is also a M-sequence with length 255. For example,

${d_{SSS}(n)} = \{ {{\begin{matrix}{{{c(n)}*( {{2*{d_{M}^{({u,v})}(n)}} - 1} )},{n = 0},1,\ldots \;,126} \\{{{c( {n + 1} )}*( {{2*{d_{M}^{({u,v})}( {n + 1} )}} - 1} )},{n = 127},\ldots \;,253}\end{matrix}\mspace{14mu} {and}\mspace{14mu} {c(n)}} = {\overset{\sim}{c}( {( {n + N_{ID}^{(2)}} )\mspace{14mu} {mod}\mspace{14mu} 255} )}} $

where N_(ID) ⁽²⁾ is cell ID in NR-PSS and {tilde over (c)}(n) can beconstructed based one of the M-sequence specified in TABLE 3 (must bedifferent from the ones generating d_(M) ^((u,v))) according to {tildeover (c)}(n)=1−2*d_(M)(n).

TABLE 9 Combination of U and V U V |U| = ┌1000/(N_(PSS) * 255)┐, e.g. U= |V| = 255, e.g. V = {1, 2, . . . , ┌1000/N_(PSS) * 255)┐} {0, 1, . . ., 254} |U| = 2 * ┌1000/(N_(PSS) * 255)┐, e.g. U = |V| = 128, e.g. V ={1, 2, . . . , 2 * ┌1000/(N_(PSS) * 255)┐} {0, 2, . . . , 254} or {0, 1,. . . , 127}

In another embodiment, if NR-SSS carries part of or the whole cell IDhypotheses as well as timing information (e.g. SS block timing index orpart of the SS block timing index), then the combination of u and v maybe large enough to cover the number of cell ID hypotheses together withtiming hypotheses (e.g. N_(SSS)·N_(b)≤|U|·|V|, where |U| and |V| meanthe size of sets U and V correspondingly, and N_(b) is the number oftiming hypotheses carried by NR-SSS). The mapping of N_(ID) ⁽¹⁾(0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) and I_(b) (0≤I_(b)≤N_(b)−1) to u and v isaccording to u=U(└(N_(ID) ⁽¹⁾·N_(b)+I_(b))/|V|┘+1) and v=V(((N_(ID)⁽¹⁾·N_(b)+I_(b))mod |V|)+1), or u=U(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|V|┘+1)and v=V(((N_(ID) ⁽¹⁾·N_(b)+I_(b) N_(SSS)) mod V|)+1), or v=V(└(N_(ID)⁽¹⁾·N_(b)+I_(b))/|U|┘+1) and u=U(((N_(ID) ⁽¹⁾·N_(b)+I_(b)) mod |U|)+1),or v=V(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|U|┘+1) and u=U(((N+I_(b)·N_(SSS))mod |U|)+1) where the set U can be a subset of {1, . . . , 16}considering the sequences' maximum cross-correlation within the set, andset V can be a subset of {0, 1, . . . , 254}. For N_(SSS)=1000 (orapproximately 1000), and for different value of N_(b), the followingcombination of U and V in TABLE 10 can be used.

TABLE 10 Combination of U and V N_(b) U V 2 |U| = 8, e.g. U = {1, 2, 3,4, |V| = 255, e,g, V = 5, 6, 7, 8} {0, 1, . . . , 254} 2 |U| = 16, e.g.U = {1, 2, 3, 4, |V| = 128, e.g. V = 5, 6, 7, 8, 9, 10, 11, 12, 13, {0,2, . . . , 254} 14, 15, 16,} or {0, 1, . . . , 127} 4 |U| = 16, e.g. U ={1, 2, 3, 4, |V| = 255, e,g, V = 5, 6, 7, 8, 9, 10, 11, 12, 13, {0, 1, .. . , 254} 14, 15, 16}

The sequence d_(SSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \;,253,{k = {{n - 127 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 17}},\ldots \;,{- 1},{L_{SSS} - 1},\ldots \;,270,{k = {n - 127 + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-SSS is transmitted.

In one embodiment of option 4, length-127 M-sequences with cyclicshifts, the sequence d_(SSS)(n) used for NR-SSS is generated from a BPSKmodulated frequency-domain M-sequence d_(M)(m) with length 127 as inoption 3 of component II.B, but mapped to central and interleavedsubcarriers within the 288 subcarriers. For example, the length-127NR-SSS sequence is mapped to even subcarrier #14, #16, . . . , #266(subcarrier starting with #0). For another example, the length-127NR-SSS sequence is mapped to even subcarrier #12, #14, . . . , #264(subcarrier starting with #0). For yet another example, the length-127NR-SSS sequence is mapped to odd subcarrier #13, #15, . . . , #265(subcarrier starting with #0). For yet another example, the length-127NR-SSS sequence is mapped to odd subcarrier #11, #13, . . . , #263(subcarrier starting with #0).

In some embodiments of component I.B, design of One-port NR-SSS Sequencefor 144 REs, the maximum number of resource elements available withinone OFDM symbol for transmitting NR-SSS is 144 (equivalent to 12 RBs),which corresponds to (note that the bandwidth contains guard band, andactual transmission bandwidth can be a little bit smaller): frequencyrange A associated with 15 kHz subcarrier spacing and 2.5 MHz NR-PSStransmission bandwidth (including guard band); frequency range Bassociated with 30 kHz subcarrier spacing and 5 MHz NR-PSS transmissionbandwidth (including guard band); frequency range C associated with 60kHz subcarrier spacing and 10 MHz NR-PSS transmission bandwidth(including guard band); frequency range D associated with 120 kHzsubcarrier spacing and 20 MHz NR-PSS transmission bandwidth (includingguard band); and frequency range E associated with 240 kHz subcarrierspacing and 40 MHz NR-PSS transmission bandwidth (including guard band).

For example, frequency range A can be around 0 to 2 GHz, frequency rangeB can be around 2 to 6 GHz, frequency range D can be above 6 GHz. Foranother example, frequency range A can be around 0 to 2 GHz, frequencyrange B can be around 2 to 6 GHz, frequency range E can be above 6 GHz.For yet another example, frequency range A can be around 0 to 6 GHz,frequency range D can be above 6 GHz. For yet another example, frequencyrange A can be around 0 to 6 GHz, frequency range E can be above 6 GHz.

In one embodiment, the same NR-SSS sequence(s) is utilized for thefrequency ranges A to E by scaling the subcarrier spacing. Note that thenumerology of NR-SSS can be different from data multiplexed in the samesymbol, so guard band is needed on both side of NR-SSS sequence infrequency domain, and the size of guard band is around 10% (whichcorrespond to around 14 REs in this sub-embodiment) such that themaximum number of REs for transmitting NR-SSS may be reduced to around130, and the same as NR-PSS. Based on this consideration, the design ofone-port based NR-SSS sequence can be selected as one of the followingoptions.

In one embodiment of option 1, interleaved two M-sequences, for thedesign of one-port based NR-SSS sequence for 144 REs using M-sequences,the NR-SSS sequence is with length 126, and the sequence d_(SSS)(0), . .. , d_(SSS)(125) is an interleaved concatenation of two length-63 binarysequences, where each of the binary sequence is constructed based onlength-63 M-sequences. The concatenated sequence is scrambled with ascrambling sequence using the cell ID information in NR-PSS if there issuch information in NR-PSS, or scrambled by an all one sequence(equivalent as no scrambling) or a common scrambling sequence for allcell ID if there is no cell ID information in NR-PSS.

More precisely, the combination of two length-63 sequences defining theNR-SSS is according to d_(SSS)(2n)=s_(m) ₀ (n)c₀(n)z_(x)(n) andd_(SSS)(2n+1)=s_(m) ₁ (n)c₁(n)z_(y)(n) where 0≤n≤62, and the particularmeaning of parameters and sequences in the equations are detailed asfollow.

In one embodiment, NR-SSS only carries part of or the whole cell IDinformation and no timing information, or NR-SSS carries both part of orthe whole cell ID information and timing information, but timinginformation is carried by z_(x)(n), then the number of hypotheses to besupported by the combination of m₀ and m₁ is N_(SSS) (note thatN_(SSS)·N_(PSS) is the number of cell ID in this case). The combinationof m₀ and m₁ to represent a hypotheses H can be according to (equivalentto TABLE 11) m₀=m′ mod 63,

${m_{1} = {( {m_{0} + \lfloor \frac{m^{\prime}}{63} \rfloor + 1} )\mspace{14mu} {mod}\mspace{14mu} 63}},{m^{\prime} = {H + {{q( {q + 1} )}\text{/}2}}},{q = \lfloor \frac{H + {q\; {\prime ( {q^{\prime} + 1} )}\text{/}2}}{62} \rfloor},{q^{\prime} = \lfloor \frac{H}{63} \rfloor},$

and the N_(SSS) cell ID hypotheses can be selected from the 1953hypotheses.

In one sub-embodiment, N_(ID) ⁽¹⁾ can be chosen as the first N_(SSS)hypotheses in TABLE 11, i.e., H=N_(ID) ⁽¹⁾ for 0≤N_(ID) ⁽¹⁾≤N_(SSS)−1.In another sub-embodiment, N_(ID) ⁽¹⁾ can be uniformed selected from the1953 hypotheses in TABLE 11, e.g. H=a Ng)+b for 0≤N_(ID) ⁽¹⁾·N_(SSS)−1,and a can be 2 or 3 or . . . or └1953/N_(SSS)┘, and b can be 0 or 1 or .. . or a−1.

TABLE 11 Hypotheses H m₀ m₁ H m₀ m₁ H m₀ m₁ H m₀ m₁  0  0  1 123  0  3 .. . . . . . . . . . . . . . . . .  1  1  2 124  1  4 . . . . . . . . . .. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1948 0 60  61 61 126 182 59 62 . . . . . . . . . 1949 1 61  62  0  2 183 0  4 . . . . . . . . . 1950 2 62  63  1  3 184  1  5 . . . . . . . . .1951 0 61 . . . . . . . . . . . . . . . . . . . . . . . . . . . 1952 162 122 60  62 241 58 62 . . . . . . . . . 1953 0 62

In another embodiment, NR-SSS carries both part of or the whole cell IDinformation and timing information, and the number of hypotheses to besupported by the combination of m₀ and m₁ is N_(SSS)·N_(b) (note thatN_(SSS)·N_(PSS) is the number of cell ID in this case), where N_(b) isthe number of timing information hypotheses to be carried by thecombination of m₀ and m₁. For example, in single beam system, if NR-SSScarries timing information indicating the NR-SSS symbol index whenmultiple NR-SSS are transmitted within a radio frame (similar to LTEspecification), then N_(b) can be the number of possible positions ofNR-SSS within a radio frame. For another example, in multiple beamsystem, N_(b) can be the number of SS block timing index to be indicatedby current NR-SSS (note that it can be the whole SS block timing indexinformation or part of it). The combination of m₀ and m₁ to represent ahypotheses H can be the same as the previous embodiment (also equivalentto TABLE 11) and the N_(SSS)·N_(b) hypotheses can be selected from the8001 hypotheses in TABLE 11. In one sub-embodiment, the combination ofcell ID hypothesis N_(ID) ⁽¹⁾ and timing index I_(b) can be chosen asthe first N_(SSS)·N_(PSS) hypotheses in TABLE 11, e.g. H=N_(b)·N_(ID)⁽¹⁾+I_(b) for 0≤N_(ID) ⁽¹⁾≤N_(SSS)−1 and 0 I_(b)≤N_(b)−1, orH=I_(b)·N_(SSS)+N_(ID) ⁽¹⁾ for 0≤N_(ID) ⁽¹⁾≤N_(SSS)−1 and0≤I_(b)≤N_(b-1).

The two sequences s_(m) ₀ (n) and s_(m) ₁ (n) are defined as twodifferent cyclic shifts of the M-sequence {tilde over (s)}(n) withlength 127 according to s_(m) ₀ (n)={tilde over (s)}((n+m) mod 63) ands_(m) ₁ (n)={tilde over (s)}((n+m₁) mod 63), and {tilde over (s)}(n) canbe constructed based one of the M-sequence specified in TABLE 12according to {tilde over (s)}(n)=1−2*d_(M)(n) for 0≤n≤62 with a properinitial condition. For example, No. 1 in TABLE 12 is utilized, thend_(M)(i+6)=[d_(M)(i+5)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

For another example, No. 2 in TABLE 12 is utilized, thend_(M)(i+6)=[d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

TABLE 12 Recursive construction method Recursive constructionCorresponding Corresponding No. method polynomial taps of register  1d_(M)(i + 6) = [d_(M)(i + 5) + x⁶+ x⁵ + 1 [1, 6] d_(M)(i)]mod 2, 0 ≤ i ≤56  2 d_(M)(i + 6) = [d_(M)(i + 1) + x⁶+ x + 1 [5, 6] d_(M)(i)]mod 2, 0≤ i ≤ 56  3 d_(M)(i + 6) = [d_(M)(i + 5) + x⁶ + x⁵ + x⁴ + [1, 2, 5, 6]d_(M)(i + 4) + d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 56  4d_(M)(i + 6) = [d_(M)(i + 5) + x⁶ + x⁵ + x² + [1, 4, 5, 6] d_(M)(i +2) + d_(M)(i + 1) + x + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 56  5 d_(M)(i + 6) =[d_(M)(i + 5) + x⁶ + x⁵ + x³ + [1, 3, 4, 6] d_(M)(i + 3) + d_(M)(i +2) + x² + 1 d_(M)(i)]mod 2, 0 ≤ i ≤ 56  6 d_(M)(i + 6) = [d_(M)(i + 4) +x⁶ + x⁴ + x³ + [2, 3, 5, 6] d_(M)(i + 3) + d_(M)(i + 1) + x + 1d_(M)(i)]mod 2, 0 ≤ i ≤ 56

In one embodiment, the two scrambling sequences c₀(n) and c₁(n) dependon the cell ID information in NR-PSS (e.g. N_(ID) ⁽²⁾) and note thateven no cell ID information is carried by NR-PS, the construction methodin this embodiment still work by considering N_(ID) ⁽²⁾=0) and aredefined by different cyclic shifts of the M-sequence {tilde over (c)}(n)with length 63 according to c₀(n)={tilde over (c)}(n+N mod 63 andc₁(n)={tilde over (c)}((n+_(ID) ⁽²⁾+N_(PSS)) mod 63 where N_(PSS) is thenumber of NR-PSS sequences (or equivalent to the number of hypotheses ofcell ID carried by NR-PSS), and {tilde over (c)}(n) can be constructedbased one of the M-sequence specified in TABLE 12 (must be differentfrom the one generating {tilde over (s)}(n)) according to {tilde over(c)}(n)=1−2*d_(M)(n) for 0≤n≤62 with a proper initial condition. Forexample, if No. 1 in TABLE 12 is utilized for generating {tilde over(s)}(n), then No. 2 can be utilized for generating {tilde over (c)}(n)as d_(M)(i+6)=[d(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(3)=d_(M)(4)=, d_(M)(5)=1.

For another example, No. 2 in TABLE 12 is utilized for generating {tildeover (s)}(n), then No. 1 can be utilized for generating {tilde over(c)}(n) as d_(M)(i+6)=[d(i+5)+d(i)]mod 2, 0≤i≤63 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In another embodiment, if there is no cell ID information is carried byNR-PSS, the two scrambling sequences c₀(n) and c₁(n) can be independentfrom cell ID information in NR-PSS and constructed the same way usingM-sequence {tilde over (c)}(n) with length 63 according toc₀(n)=c₁(n)={tilde over (c)}(n) where {tilde over (c)}(n) can beconstructed based one of the M-sequence specified in TABLE 12 (must bedifferent from the one generating {tilde over (s)}(n)) according to{tilde over (c)}(n)=1−2*d_(M)(n) for 0≤n≤62 with a proper initialcondition. For example, if No. 1 in TABLE 12 is utilized for generating{tilde over (s)}(n), then No. 2 can be utilized for generating {tildeover (c)}(n) as d_(M)(i+6)=[d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

For another example, No. 2 in TABLE 12 is utilized for generating {tildeover (s)}(n), then No. 1 can be utilized for generating {tilde over(c)}(n) as d_(M)(i+6)=[d(i+5)+d(i)]mod 2, 0≤i≤63 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In yet another embodiment, if there is no cell ID information is carriedby NR-PSS, the two scrambling sequences c₀(n) and c₁(n) can beindependent from cell ID information in NR-PSS and constructed the sameway according to c₀(n)=c₁(n)=1 which is equivalent to no scramblingsequence performed.

In one embodiment, the sequence z_(x)(n) and z_(y) (n) are based on thecell ID information in NR-PSS (in this case x=m₁ and y=m₀), and definedby a cyclic shift of the M-sequence {tilde over (z)}(n) with length-63according to z_(y)(n)=z_(m) ₀ (n)=2((n+(m₀ mod z)) mod 63) andz_(x)(n)=z_(m) ₁ (n)={tilde over (z)}((n+(m₁ mod z)) mod 63) where z isa parameter related the total number of hypotheses carried bycombination of m₀ and m₁ (can refer to number of cell ID hypotheses orcombination of cell ID and timing information), and {tilde over (z)}(n)can be constructed based on one of the M-sequence specified in TABLE 12(must be different from the ones generating {tilde over (s)}(n) and{tilde over (c)}(n)) according to {tilde over (z)}(n)=1−2*d_(M)(n) for0≤n≤62 with a proper initial condition. For example, if No. 1 in TABLE12 is utilized for generating {tilde over (s)}(n), and No. 2 is utilizedfor generating {tilde over (c)}(n), then No. 6 can be utilized forgenerating {tilde over (z)}(n) with a proper initial conditiond_(M)(i+6)=[d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1) d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

For another example, if No. 2 in TABLE 12 is utilized for generating{tilde over (s)}(n), and No. 1 is utilized for generating {tilde over(c)}(n), then No. 5 can be utilized for generating {tilde over (z)}(n)with a proper initial condition d_(M)(i+6)[d(i+5)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In another embodiment, one of the sequence z_(x)(n) and z_(y)(n) arebased on the cell ID information in NR-PSS (in this case y=m₀), anddefined by a cyclic shift of the M-sequence {tilde over (z)}(n) withlength-63 according to z_(x)(n)=1 and z_(y) (n)=z_(m) ₀ (n)={tilde over(z)}((n+(m₀ mod z)) mod 63) where z is a parameter related the totalnumber of hypotheses carried by combination of m₀ and m₁ (can refer tonumber of cell ID hypotheses or combination of cell ID and timinginformation), and {tilde over (z)}(n) can be constructed based on one ofthe M-sequence specified in TABLE 12 (must be different from the onesgenerating {tilde over (s)}(n) and {tilde over (c)}(n)) according to{tilde over (z)}(n)=1−2*d_(M)(n) for 0≤n≤62 with a proper initialcondition. For example, if No. 1 in TABLE 12 is utilized for generating{tilde over (s)}(n), and No. 2 is utilized for generating {tilde over(c)}(n), then No. 6 can be utilized for generating {tilde over (z)}(n)with a proper initial conditiond_(M)(i+6)=[d(i+4)+d_(M)(i+3)+d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1) d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In another example, if No. 2 in TABLE 12 is utilized for generating{tilde over (s)}(n), and No. 1 is utilized for generating {tilde over(c)}(n), then No. 5 can be utilized for generating {tilde over (z)}(n)with a proper initial condition d_(M)(i+6)[d(i+5)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In yet another embodiment, the sequence z_(x)(n) and z_(y)(n) are basedon the timing information, e.g. part of or the whole SS block timingindex I_(b) (in this case x=y=b), and defined by a cyclic shift of theM-sequence {tilde over (z)}(n) with length-63 according toz_(x)(n)=z_(y)(n)=z_(b)(n)={tilde over (z)}((n+b) mod 63) where {tildeover (z)}(n) can be constructed based on one of the M-sequence specifiedin TABLE 12 (must be different from the ones generating {tilde over(s)}(n) and {tilde over (c)}(n)) according to {tilde over(z)}(n)=1−2*d_(M)(n) for 0≤n≤62 with a proper initial condition. Forexample, if No. 1 in TABLE 12 is utilized for generating {tilde over(s)}(n), and No. 2 is utilized for generating {tilde over (c)}(n), thenNo. 6 can be utilized for generating {tilde over (z)}(n) with a properinitial conditiond_(M)(i+6)=[d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In yet another example, if No. 2 in TABLE 12 is utilized for generating{tilde over (s)}(n), and No. 1 is utilized for generating {tilde over(c)}(n), then No. 5 can be utilized for generating {tilde over (z)}(n)with a proper initial condition d_(M)(i+6)[d(i+5)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In yet another embodiment, one of the sequence z_(x)(n) and z_(y)(n) arebased on the timing information, e.g. part of or the whole SS blocktiming index I_(b) (in this case e.g. y=b), and defined by a cyclicshift of the M-sequence {tilde over (z)}(n) with length-63 according toz_(x)(n)=1 and z_(y)(n)=z_(b)(n)=2((n+b) mod 63) where {tilde over(z)}(n) can be constructed based on one of the M-sequence specified inTABLE 12 (must be different from the ones generating {tilde over (s)}(n)and {tilde over (c)}(n)) according to {tilde over (z)}(n)=1−2*d_(M)(n)for 0≤n≤62 with a proper initial condition. For example, if No. 1 inTABLE 12 is utilized for generating {tilde over (s)}(n), and No. 2 isutilized for generating {tilde over (c)}(n), then No. 6 can be utilizedfor generating {tilde over (z)}(n) with a proper initial conditiond_(M)(i+6)=[d_(M)(i+4)+d_(M)(i+3)+d_(M)(i+1)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In another example, if No. 2 in TABLE 12 is utilized for generating{tilde over (s)}(n), and No. 1 is utilized for generating {tilde over(c)}(n), then No. 5 can be utilized for generating {tilde over (z)}(n)with a proper initial condition d_(M)(i+6)[d(i+5)+d_(M)(i+3)+d_(M)(i+2)+d_(M)(i)]mod 2, 0≤i≤56 andd_(M)(0)=d_(M)(1)=d_(M)(2)=d_(M)(3)=d_(M)(4)=0, d_(M)(5)=1.

In yet another embodiment, the sequence z_(x)(n) is not related to thecell ID information or timing information, and is defined by z_(x)(n)=1for 0≤n≤62 which is equivalent to no scrambling sequence performed.

The sequence d_(SSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \;,125,{k = {{n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- 9}},\ldots \;,{- 1},126,\ldots \;,134,{k = {n - 63 + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-SSS is transmitted.

In one embodiments of option 2, ZC-sequences with cyclic shifts, for thedesign of one-port based NR-SSS sequence for 144 REs using ZC-sequenceswith cyclic shifts, defining the NR-SSS is according to

${d_{SSS}(n)} = \{ \begin{matrix}{{d_{ZC}^{({u,v})}(n)},{n = 0},1,\ldots \;,\frac{L_{PSS} - 3}{2}} \\{{d_{ZC}^{({u,v})}( {n + 1} )},{n = \frac{L_{PSS} - 1}{2}},\ldots \;,{L_{PSS} - 2}}\end{matrix} $

where L_(SSS) is the length of NR-SSS sequence, and L_(SSS) is an oddnumber smaller than 130. For example, L_(SSS)=127. For another example,L_(SSS)=129. d_(ZC) ^((u,v))(n) is a length-L_(SSS) ZC-sequence withroot index u∈U and cyclic shift value v∈V, according to

${{d_{ZC}^{({u,v})}(n)} = {{{d_{ZC}^{(u)}( {( {n + v} ){mod}\; L_{SSS}} )}\mspace{14mu} {and}\mspace{14mu} d_{ZC}^{(u)}} = {{e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{L_{SSS}}}\mspace{14mu} {for}\mspace{14mu} n} = 0}}},1,\ldots \;,{L_{SSS} - 1.}$

In one embodiment, if NR-SSS only carries part of or the whole cell IDhypotheses, then the combination of u and v may be large enough to coverthe number of cell ID hypotheses (e.g. N_(SSS)≤|U|·|V|, where |U| and|V| mean the size of sets U and V correspondingly). The mapping ofN_(ID) ⁽¹⁾ (0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) to u and v is according tou=U(└N_(ID) ⁽¹⁾/|V|┘+1) and v=V((N_(ID) ⁽¹⁾ mod |V|)+1), or v=V([N_(ID)⁽¹⁾)/|U|]+1) and u=U((N_(ID) ⁽¹⁾ mod |U|)+1) where the set U can be asubset of {0, 1, . . . , 126} when L_(SSS)=255 considering thesequences' maximum cross-correlation within the set, and set V can be asubset of {0, 1, . . . , 126}. For N_(SSS)=1000 (or approximately 1000),the following combination of U and V in TABLE 13 can be used forL_(SSS)=127.

TABLE 13 Combination of U and V U V |U| = 8, e.g. U = {53, 55, 57, |V| =127, e,g, V = 59, 68, 70, 72, 74} {0, 1, . . . , 126} |U| = 16, e.g. U ={53, 54, . . . , |V| = 64, e.g. V = 60, 67, 68, . . . , 74} {0, 2, . . ., 126} or {0, 1, . . . , 63}

In another embodiment, if NR-SSS carries part of or the whole cell IDhypotheses as well as timing information (e.g. SS block timing index orpart of the SS block timing index), then the combination of u and v maybe large enough to cover the number of cell ID hypotheses together withtiming hypotheses (e.g. N_(SSS)·N_(b)≤|U|·|V|, where |U| and |V| meanthe size of sets U and V correspondingly, and N_(b) is the number oftiming hypotheses carried by NR-SSS). The mapping of NM (0≤N_(ID)⁽¹⁾≤N_(SSS)−1) and I_(b) (0≤I_(b)≤N_(b)−1) to u and v is according tou=U(└(N_(ID) ⁽¹⁾·N_(b)+I_(b))/|V|┘+1) and v=V(((N_(ID)⁽¹⁾·N_(b)+I_(b))mod V|)+1), or u=U(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|V|┘+1)and v=V(((N_(ID) ⁽¹⁾·N_(b)+I_(b)·N_(SSS)) mod V)+1), or v=V(└(N_(ID)⁽¹⁾·N_(b)+I_(b))/|U|+1) and u=U(((N_(ID) ⁽¹⁾·N_(b)+I_(b)) mod |U|)+1),or v=V(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|U|┘+1) and u=U(((N+I_(b)·N_(SSS))mod |U|)+1) where the set U can be a subset of {0, 1, . . . , 126} whenL_(SSS)=127 considering the sequences' maximum cross-correlation withinthe set, and set V can be a subset of {0, 1, . . . , 126}. ForN_(SSS)=1000 (or approximately 1000), and for different value of N_(b),the following combination of U and V in TABLE 14 can be used forL_(SSS)=127.

TABLE 14 Combination of U and V N_(b) U V 2 |U| = 16, e.g. U = {53, |V|= 127, e,g, V = 54, . . . , 60, 67, 68, . . . , 74} {0, 1, . . . , 126}2 |U| = 32, e.g. U = |V| = 64, e.g. V = {48, 49, . . . , 78, 79} {0, 2,. . . , 126} or {0, 1, . . . , 63} 4 |U| = 32, e.g. U = |V| = 127, e,g,V = {48, 49, . . . , 78, 79} {0, 1, . . . , 126} 4 |U| = 64, e.g. U =|V| = 64 , e.g. V = {32, 33, . . . , 94, 95} {0, 2, . . . , 126} or {0,1, . . . , 63} 8 |U| = 64, e.g. U = |V| = 127, e,g, V = {32, 33, . . . ,94, 95} {0, 1, . . . , 126} 8 |U| = 127, e.g. U = |V| = 64, e.g. V = {0,1, . . . , 126} {0, 2, . . . , 126} or {0, 1, . . . , 63} 4 |U| = 127,e.g. U = |V| = 127, e.g. V = {0, 1, . . . , 126} {0, 1, . . . , 126}

The sequence d_(SSS)(n) is mapped to the resource elements according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \;,{L_{SSS} - 2},{k = {{n - \frac{L_{SSS} - 1}{2} + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}\mspace{14mu} a_{k,l}}} = 0}},{n = {- \frac{144 - L_{SSS} + 1}{2}}},\ldots \;,{- 1},{L_{SSS} - 1},\ldots \;,{\frac{144 + L_{SSS} + 1}{2} - 2},{k = {n - \frac{L_{SSS} - 1}{2} + \frac{N_{RB}N_{SC}}{2}}}$

where N_(RB) is number of total RBs for transmission, and N_(SC) is thenumber of subcarriers within a RB (e.g. N_(SC)=12). l corresponds to theOFDM symbol index where NR-SSS is transmitted.

In one embodiment of Option 3, M-sequences with cyclic shifts, for thedesign of one-port based NR-SSS sequence for 144 REs usingfrequency-domain BPSK modulated length-127 M-sequences with cyclicshifts, where the cyclic shifts are determined by the combination ofcell ID hypotheses carried by NR-SSS, or the combination of cell IDhypotheses carried by NR-PSS and NR-SSS.

In one embodiment, defining the NR-SSS is according to

${d_{SSS}(n)} = \{ \begin{matrix}{{{2*{d_{M}^{({u,v})}(n)}} - 1},{n = 0},1,\ldots \;,62} \\{{{2*{d_{M}^{({u,v})}( {n + 1} )}} - 1},{n = 63},\ldots \;,125}\end{matrix} $

where d_(M) ^((u,v))(n) is a length-127 M-sequence with number index uand cyclic shift value v∈V, according to d_(M) ^((u,v))(n)=d_(M)^((u))((n+v)mod 127) and d_(M) ^((u)) is the No. u (1≤u≤18) sequencedefined in TABLE 4.

In one embodiment, if NR-SSS only carries part of or the whole cell IDhypotheses, then the combination of u and v may be large enough to coverthe number of cell ID hypotheses in NR-SSS (e.g. N_(SSS)≤|U|·|V|, where|U| and |V| mean the size of sets U and V correspondingly). The mappingof N_(ID) ⁽¹⁾ (0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) to u and v is according to

${{ { {u = {U( {\lfloor {N_{ID}^{(1)}\text{/}} V} }} \rfloor + 1} )\mspace{14mu} {and}\mspace{14mu} v} = {V( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {V}} ) + 1} )}},{{{or}\mspace{14mu} v} = {{{V( {\lfloor \frac{N_{ID}^{(1)}}{U} \rfloor + 1} )}\mspace{14mu} {and}\mspace{14mu} u} = {U( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {U}} ) + 1} )}}}$

where the set U can be a subset of {1, . . . , 18} considering thesequences' maximum cross-correlation within the set, and set V can be asubset of {0, 1, . . . , 126}. For N_(SSS)=1000 (or approximately 1000),the following combination of U and V in TABLE 15 can be used.

TABLE 15 Combination of U and V U V |U| = 8, e.g. U = |V| = 127, e.g. V= {1, 2, 3, 4, 5, 6, 7, 8} {0, 1, . . . , 126} |U| = 18, e.g. U = |V| =64, e.g. V = {1, 2, . . . , 17, 18} {0, 2, . . . , 126} or {0, 1, . . ., 63}

In one embodiment, if NR-SSS carries part of cell ID hypotheses, and for

$N_{SSS} = \frac{1000}{N_{PSS}}$

(or approximately

$\frac{1000}{N_{PSS}},$

where N_(PSS) is the number of NR-PSS sequences), the followingcombination of U and V in TABLE 16 can be used, where the mapping of N)(0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) to u and v is according to

${u = {{{U( {\lfloor \frac{N_{ID}^{(1)}}{V} \rfloor + 1} )}\mspace{14mu} {and}\mspace{14mu} v} = {V( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {V}} ) + 1} )}}},{{{or}\mspace{14mu} v} = {{{V( {\lfloor \frac{N_{ID}^{(1)}}{U} \rfloor + 1} )}\mspace{14mu} {and}\mspace{14mu} u} = {{U( {( {N_{ID}^{(1)}\mspace{14mu} {mod}\mspace{14mu} {U}} ) + 1} )}.}}}$

In this case, a scrambling sequence can be applied to represent the cellID in NR-PSS, where the scrambling sequence is also a M-sequence withlength 127. For example,

${d_{SSS}(n)} = \{ \begin{matrix}{{{c(n)}*( {{2*{d_{M}^{({u,v})}(n)}} - 1} )},{n = 0},1,\ldots \;,62} \\{{{c( {n + 1} )}*( {{2*{d_{M}^{({u,v})}( {n + 1} )}} - 1} )},{n = 63},\ldots \;,125}\end{matrix} $

and {tilde over (c)}(n)={tilde over (c)}((n+C·N_(ID) ⁽²⁾) mod 127) andd_(M) ^((u,v))(n)=d(((n+v)mod 127) where N_(ID) ⁽²⁾ is cell ID in NR-PSSand {tilde over (c)}(n) can be constructed based one of the M-sequencespecified in TABLE 4 (must be different from the ones generating d_(M)^((u,v))) according to {tilde over (c)}(n)=1−2*d_(M)(n), and C is apositive integer, e.g. C=1 (shifts are 0, 1, 2 in case of N_(PSS)=3) orC=43 (shifts are 0, 43, 86 in case of N_(PSS)=3).

TABLE 16 Combination of U and V U V |U| = ┌1000/(N_(PSS) * 127)┐, e.g. U= |V| = 127, e.g. V = {0,1, ..., 126} {1,2, ..., ┌1000/(N_(PSS) * 127)┐}or other set such that correlation is minimized |U| = 2 *┌1000/(N_(PSS) * 127)┐, e.g. U = |V| = 64, e.g. V = {0,2, ..., 126}{1,2, ..., 2 * ┌1000/(N_(PSS) * 127)┐} or or other set such thatcorrelation is {0,1, ..., 63} minimized

In the case of N_(PSS)=3, |U|=3 and |V|=127, 3 M-sequences (each with127 shifts) are scrambled by another M-sequence to generate the SSSsequences. In one sub-embodiment, the scrambling sequence {tilde over(c)}(n) can be the same as NR-PSS sequences (if NR-PSS is constructed byshifts of one M-sequence, e.g. using No. 3 M-sequence in TABLE 4), andthe 3 M-sequences are chosen such that the cross-correlation amongNR-SSS sequences and cross-correlation between NR-PSS and NR-SSS areminimized. For example, U={1, 9, 14}.

In one embodiment, if NR-SSS carries part of cell ID hypotheses, and for

$N_{SSS} = \frac{1000}{N_{PSS}}$

(or approximately

$\frac{1000}{N_{PSS}},$

where N_(PSS) is the number of NR-PSS sequences), the construction ofNR-SSS is given in frequency domain by a product of two BPSK modulatedM-sequences with cyclic shifts, where the cyclic shifts are determinedby the combination of cell ID hypotheses carried by both NR-PSS andNR-SSS. For example,

${d_{SSS}(n)} = \{ \begin{matrix}{{( {{2*{d_{M}^{({{u\; 1},{v\; 1}})}(n)}} - 1} )*( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}(n)}} - 1} )},{n = 0},1,\ldots \;,62} \\{{( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}( {n + 1} )}} - 1} )*( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}( {n + 1} )}} - 1} )},{n = 63},\ldots \;,125}\end{matrix} $

if the DC subcarrier is truncated, and d_(SSS)(n)=(2*d_(M)^((u1,v1))(n)−1)*(2*d_(M) ^((u2,v2))(n)−1), n=0, 1, . . . , 126 if theDC subcarrier is not truncated, and d_(M) ^((u1,v1))(n)=d_(M)((n+v1)mod127) and d_(M) ^((u2,v2))(n)=d_(M) ((n+v2)mod 127) where the cyclicshifts v1, v2 are based on the cell ID N) (cell ID in NR-PSS) and NJ(cell ID in NR-SSS). For example, choosing one of the M-sequencegenerator index u1=3 (corresponding M-sequence specified in TABLE 4, andinitial condition after TABLE 4), choosing the other M-sequencegenerator index u2=2 (corresponding M-sequence specified in TABLE 4, andinitial condition after TABLE 4), and v1∈V1={0, 15, 30, 45, 60, 75, 90,105, 120} or V1={0, 1, 2, 3, 4, 5, 6, 7, 8}, and v2∈V2={0, 1, . . . ,126}, and v2=V2((N_(ID) ⁽¹⁾ mod 127)+1) and

${v\; 1} = {V\; 1{( {{\lfloor \frac{N_{ID}^{(1)}}{127} \rfloor \cdot 3} + 1} ).}}$

In another embodiment, if NR-SSS carries part of or the whole cell IDhypotheses as well as timing information (e.g. SS block timing index orpart of the SS block timing index), then the combination of u and v maybe large enough to cover the number of cell ID hypotheses together withtiming hypotheses (e.g. N_(SSS)·N_(b)≤|U|·|V|, where |U| and |V| meanthe size of sets U and V correspondingly, and N_(b) is the number oftiming hypotheses carried by NR-SSS). The mapping of N_(ID) ⁽¹⁾(0≤N_(ID) ⁽¹⁾≤N_(SSS)−1) and I_(b) (0≤I_(b)·N_(b)−1) to u and v isaccording to u=U(└(N_(ID) ⁽¹⁾·N_(b)+I_(b))/|V|┘+1) and v=V(((N_(ID)⁽¹⁾·N_(b)+I_(b)) mod V|)+1), or u=U(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|V|┘+1)and v=V(((N_(ID) ⁽¹⁾·N_(b)+I_(b) N_(SSS)) mod V|)+1), or v=V(└(N_(ID)⁽¹⁾·N_(b)+I_(b))/|U|┘+1) and u=U(((N_(ID) ⁽¹⁾·N_(b)+I_(b)) mod |U|)+1),or v=V(└(N_(ID) ⁽¹⁾+I_(b)·N_(SSS))/|U|┘+1) and u=U(((N+I_(b)·N_(SSS))mod |U|)+1) where the set U can be a subset of {1, . . . , 18}considering the sequences' maximum cross-correlation within the set, andset V can be a subset of {0, 1, . . . , 126}. For N_(SSS)=1000 (orapproximately 1000), and for different value of N_(b), the followingcombination of U and V in TABLE 17 can be used.

TABLE 17 Combination of U and V N_(b) U V 2 |U| =18, e.g. U = {1,2, ...,17,18} |V| = 127, e.g. V = {0,1, ..., 126}

In another embodiment, if NR-SSS carries part of cell ID hypotheses aswell as timing information (e.g. first or second 5 ms within a radioframe, and/or SS block timing index or part of the SS block timingindex), and for N_(SSS)=N_(b)−1000/N_(PSS) (or approximatelyN_(b)−1000/N_(PSS), where N_(PSS) is the number of NR-PSS sequences andN_(b) is the number of timing hypotheses), the construction of NR-SSS isgiven by a product of two M-sequence with shift. For example,

${d_{SSS}(n)} = \{ \begin{matrix}{{( {{2*{d_{M}^{({{u\; 1},{v\; 1}})}(n)}} - 1} )*( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}(n)}} - 1} )},{n = 0},1,\ldots \;,62} \\{{( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}( {n + 1} )}} - 1} )*( {{2*{d_{M}^{({{u\; 2},{v\; 2}})}( {n + 1} )}} - 1} )},{n = 63},\ldots \;,125}\end{matrix} $

and d_(M) ^((u1,v1))(n)=d_(M) ^((u1))((n+v1)mod 127) and d_(M)^((u2,v2))(n)=d_(M) ^((u2))((n+v2)mod 127) where u1, u2, v1, v2 arebased on the cell ID N_(ID) ⁽²⁾ (cell ID in NR-PSS) and NM (cell ID inNR-SSS) and N_(b). For example, u1=3 (corresponding M-sequence specifiedin TABLE 4), u2=2 (corresponding M-sequence specified in TABLE 4), andv1∈V1={0, └127/9/N_(b)┘, . . . , └127/9/N_(b)┘ (9·N_(b)−1)} or V1={0, 1,. . . 9*N_(b)−1}, and v2∈V2={0, 1, . . . , 126}, and

${v\; 1} = {V\; 1( {{\lfloor \frac{N_{ID}^{(1)}}{127} \rfloor \cdot 3} + N_{ID}^{(2)} + {I_{b} \cdot 9} + 1} )}$

where I_(b) is the timing index (0≤I_(b)≤N_(b)−1).

The sequence d_(SSS)(n) is mapped to the central resource elements ofthe symbol for NR-SSS transmission according to

${a_{k,l} = {d_{SSS}(n)}},{n = 0},\ldots \mspace{14mu},125,{k = {n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}}}}$${a_{k,l} = 0},{n = {- 9}},\ldots \mspace{14mu},{- 1},{L_{sss} - 1},134,{k = {n - {63} + \frac{N_{RB}N_{SC}}{2}}}$

if the DC subcarrier is truncated, and according to

${a_{k,l} = {d_{PSS}(n)}},{n = 0},\ldots \mspace{14mu},{k = {n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {and}}}}$${a_{k,l} = 0},{n = {- 9}},\ldots \mspace{14mu},{- 1},127,\ldots \mspace{14mu},134,{k = {n - 63 + {\frac{N_{RB}N_{SC}}{2}\mspace{14mu} {or}}}}$${a_{k,l} = {d_{PSS}( {n + 1} )}},{n = {- 1}},\ldots \mspace{14mu},125,{k = {n - 63 + {\frac{N_{RB}N_{SC}}{2}a\mspace{14mu} {and}}}}$${a_{k,l} = 0},{n = {- 9}},\ldots \mspace{14mu},{- 2},126,\ldots \mspace{14mu},134,{k = {n - 63 + \frac{N_{RB}N_{SC}}{2}}}$

if the DC subcarrier is not truncated, where N_(RB) is number of totalRBs for NR-SSS transmission (e.g. N_(RB)=12), and N_(SC) is the numberof subcarriers within a RB (e.g. N_(SC)=12). l corresponds to the OFDMsymbol index where NR-SSS is transmitted. Note that in onesub-embodiment, no matter DC subcarrier is truncated or not, NR-PSS andNR-SSS are mapped to the same subcarriers in frequency domain, if theirsequence lengths are the same.

In some embodiments of component IX, NR-PSS and NR-SSS mapping fordifferent subcarrier spacing, NR-PSS and NR-SSS are mapped the same wayregardless of the subcarrier spacing value. In another embodiment, themapping method for NR-PSS and NR-SSS can be different, dependent on thesubcarrier spacing value. One applicable scenario is, if two subcarrierspacing values are supported for a given carrier frequency range, e.g. XkHz and Y kHz, the sequence of NR-PSS and NR-SSS can be the same, butmapping the sequence to subcarriers can be different corresponding toeach subcarrier spacing. For a particular example, if X=2*Y, which meansone of the subcarrier spacing supported is twice of the other one, themapping of NR-PSS and NR-SSS sequence to the subcarriers can be asfollow: for subcarrier spacing X, NR-PSS and NR-SSS are mapped to thecentral 12 PRB (144 RE sequence design), while for subcarrier spacing Y,NR-PSS and NR-SSS are mapped to the whole 24 PRB (288 RE sequencedesign) but with a interleaved/comb pattern (e.g. mapped to the odd oreven subcarrier indices only).

In this way, UE does not need to blindly decode the subcarrier spacingutilized by the NW, and can assume the default and single subcarrierspacing of X kHz (e.g. always assuming the larger subcarrier spacing)when performing the synchronization process. The actual utilizedsubcarrier spacing from the NW can be indicated to UE in thesynchronization signals (e.g. indicated by NR-PSS sequence, or by NR-SSSsequence, or NR-SSS mapping pattern) or by other signal/channel (e.g.DMRS sequence or mapping pattern for NR-PBCH, or in NR-PBCH payload (inthis case, UE needs to blindly decode the PBCH using two subcarrierspacing first)).

FIG. 28 illustrates an example mapping pattern 2800 according toembodiments of the present disclosure. The embodiment of the mappingpattern 2800 illustrated in FIG. 28 is for illustration only. FIG. 28does not limit the scope of this disclosure to any particularimplementation of the mapping pattern 2800. An illustration of themapping pattern depending on subcarrier spacing is shown in FIG. 28.

In one sub-embodiment, NR-PSS and NR-SSS are mapped to the samesubcarriers for subcarrier spacing Y. In another sub-embodiment, NR-PSSand NR-SSS are mapped to different subcarriers (e.g. one on evensubcarriers and the other on odd subcarriers). In one example, forcarrier frequency range 0 to 6 GHz, X=30 kHz, and Y=15 kHz. In anotherexample, for carrier frequency range 6 to 52.6 GHz, X=240 kHz, and Y=120kHz.

In the present disclosure, numerology refers to a set of signalparameters which can include subframe duration, sub-carrier spacing,cyclic prefix length, transmission bandwidth, or any combination ofthese signal parameters.

The present disclosure relates generally to wireless communicationsystems and, more specifically, to the design modulation scheme for NRsecondary synchronization signals (NR-SSS).

For LTE system, primary and secondary synchronization signals (PSS andSSS, respectively) are used for coarse timing and frequencysynchronization and cell ID acquisition. Since PSS/SSS is transmittedtwice per 10 ms radio frame and time-domain enumeration is introduced interms of System Frame Number (SFN, included in the MIB), frame timing isdetected from PSS/SSS to avoid the need for increasing the detectionburden from PBCH. In addition, cyclic prefix (CP) length and, ifunknown, duplexing scheme can be detected from PSS/SSS. The PSS isconstructed from a frequency-domain ZC sequence of length 63, with themiddle element truncated to avoid using the d.c. subcarrier. Three rootsare selected for PSS to represent the three physical layer identitieswithin each group of cells. The SSS sequences are based on the maximumlength sequences (also known as M-sequences). Each SSS sequence isconstructed by interleaving two length-31 BPSK modulated sequences infrequency domain, where the two source sequences before modulation aredifferent cyclic shifts of the same M-sequence. The cyclic shift indicesare constructed from the physical cell ID group.

Since PSS/SSS detection can be faulty (due to, for instance,non-idealities in the auto- and cross-correlation properties of PSS/SSSand lack of CRC protection), cell ID hypotheses detected from PSS/SSSmay occasionally be confirmed via PBCH detection. PBCH is primarily usedto signal the Master Block Information (MIB) which includes DL and ULsystem bandwidth information (3 bits), PHICH information (3 bits), andSFN (8 bits). Adding 10 reserved bits (for other uses such as MTC), theMIB payload amounts to 24 bits. After appended with a 16-bit CRC, arate-1/3 tail-biting convolutional coding, 4× repetition, and QPSKmodulation are applied to the 40-bit codeword. The resulting QPSK symbolstream is transmitted across 4 subframes spread over 4 radio frames.Other than detecting MIB, blind detection of the number of CRS ports isalso needed for PBCH.

For NR, the transmission bandwidth containing synchronization signals isexpected to be larger than LTE system, such that a new design of NRsynchronization signals, aiming for robustness against initial frequencyoffset and auto-correlation profile, is possible.

For NR, one construction method for NR-SSS can be message-based. Forexample, all information carried by NR-SSS is presented by one or moremessages, and then potentially protected with CRC(s), encoded by channelcoding codes, rate matched, modulated, precoded if multiple transmitports are utilized, and mapped to resource elements. One generalflowchart illustrating the data processing steps for message-basedNR-SSS construction is shown in FIG. 17. Note that modules or part ofthe functionalities within the modules in this flow chart can be set asdefault values such that they do not have any impact. The focus of thisdisclosure is on the modulation module (highlight 1708 in FIG. 17),where the input to this module is a sequence of binary bits, denoted ase₀ ^((i)), . . . , e_(E(i)-1) ^((i)) (1707 in FIG. 17), where the rangeof index i is the codeword index output from the previous channel codingmodule (1706 in FIG. 17) (for example, i=1, 2 for 2 codewords case, andi=1 for single codeword case). The output from modulation module is asequence of complex-valued modulated symbols, denoted as d^((i))(0), . .. , d^((i))(M(i)−1), where M(i) is the number of modulated symbols. Forexample, if the number of bits within in each modulated symbol is m(i)for codeword i, then M(i)=E(i)/m(i).

In some embodiments of component X, phase shift keying (PSK) modulationfor NR-SSS, phase shift keying (PSK) schemes use modulation signals withdifferent phases to represent different sets of bits. Several options ofPSK for NR-SSS modulation are considered here, which take one or morebinary bits in the input bit stream, denoted by b₀, b₁, . . . ,b_(m(i)-1) (m(i) is number of bits mapped to one modulated symbol forcodeword i, and b₀, b₁, . . . , b_(m(i)-1) are segment of the longsequence e₀ ^((i)), . . . , e_(E(i)-1) ^((i)) (1707 in FIG. 17)), tooutput a complex-valued modulation symbol s=I+Qj or a sequence ofsymbols, where I (inphase component) and Q (quadrature component) arereal numbers. Then the modulation signal is transmitted at the carrierfrequency f_(c), i.e., with basis function

${{\Theta (t)} = {\sqrt{\frac{2}{T_{s}}}\cos \mspace{11mu} ( {2\pi f_{c}t} )}},$

where T_(s) is the symbol duration of subcarriers.

The following options can be utilized for NR-SSS, where NR-SSS ismessage-based constructed. Note that the modulation schemes utilized fordifferent codewords within NR-SSS can be the same or different. In oneembodiment of option 1 of component X, binary phase shift keying (BPSK).In case of BPSK modulation, a single bit b₀ is mapped to the symbols=I+Qj. An example of BPSK is illustrated in TABLE 18.

TABLE 18 An example of BPSK b₀ I Q 0  1/ {square root over (2)}  1/{square root over (2)} 1 −1/ {square root over (2)} −1/ {square rootover (2)}

In another embodiment of option 2 of component X, quadrature phase shiftkeying (QPSK). In case of QPSK modulation, a pair of two bits b₀, b₁ aremapped to the symbol s=1+Qj. An example of QPSK is illustrated in TABLE19.

TABLE 19 An example of QPSK b₀b₁ I Q 00 1 0 01 −1  0 10 0 1 11 0 −1 

TABLE 20 Another example of QPSK b₀b₁ I Q 00  1/ {square root over (2)} 1/{square root over (2)} 01  1/ {square root over (2)} −1/ {square rootover (2)} 10 −1/ {square root over (2)}  1/ {square root over (2)} 11−1/ {square root over (2)} −1/ {square root over (2)}

In one embodiment of option 3 of component X, M-array phase shift keying(MPSK). In case of MPSK modulation, a group of log₂ M bits are mapped tothe M-array symbol sequence

${s = {{\exp ( {j( {{\frac{2\pi}{M}k} + \varphi_{0}} )} )} = {{\cos ( {{\frac{2\pi}{M}k} + \varphi_{0}} )} + {j\mspace{11mu} {\sin ( {{\frac{2\pi}{M}k} + \varphi_{0}} )}}}}},{k = 1},2,\ldots \mspace{14mu},M,$

where ϕ₀ is an arbitrary constant phase. Note that Option 1 and 2 can beconsidered as special cases of MPSK. For the example of BPSK mapping asTABLE 18 in Option 1, M=2,

${\varphi_{0} = {- \frac{3\pi}{4}}},$

and k=1, 2 corresponds to b₀=0, 1. For the example of QPSK mapping asTABLE 19 in Option 2, M=4,

${\varphi_{0} = {- \frac{\pi}{2}}},$

and k=1, 2, 3, 4 corresponds to b₀b₁=00, 10, 01, 11. For the example ofQPSK mapping as TABLE 20 in Option 2, M=4,

${\varphi_{0} = {- \frac{\pi}{4}}},$

and k=1, 2, 3, 4 corresponds to b₀b₁=00, 10, 11, 01. For one example of8PSK mapping, M=8, ϕ₀=0, and k=1, 2, . . . , 8 corresponds tob₀b₁b₂=000, 001, 011, 010, 011, 100, 101, 110, 111.

In one embodiment of option 4 of component X, differential phase shiftkeying (DPSK). DPSK is an example of PSK that facilitates the use ofnon-coherent demodulation, which does not require the knowledge of theactual carrier phase. This is done by differentially encoding thetransmitted bits. The differential encoding includes changing the phaseof the current transmit signal in accordance with the input bits b₀,b_(i), . . . , b_(m(i)-1) relative to the phase of the previous transmitsignal rather than to the carrier phase.

In one example is Differential BPSK (DBPSK), where the initial symbol isdenoted as x(0)=exp (jθ), and for the i^(th) input bit b_(i), where iranges from 1 to the length of the bit stream: if b_(i)=1, then phase ofthe current signal is shifted by π, i.e., x(i)=x(i−1)·exp (jπ)≡−x(i−1);if b_(i)=0, then the current signal remains the same, i.e., x(i)=x(i−1).In one case, θ=0. In another case, θ=π/4.

In another example is differential QPSK (DQPSK), where the initialsymbol is denoted as x(0)=exp (jθ), and for the i^(th) pair of inputbits b_(2i-1)b_(2i), where i ranges from 1 to half of the length of thebit stream (0 can be appended if the length is odd): ifb_(2i-1)b_(2i)=01, then phase of the current signal is shifted by π/2,i.e., x(i)=x(i−1)·exp (jπ/2); if b_(2i-1)b_(2i)=11, then phase of thecurrent signal is shifted by i, i.e., x(i)=x(i−1)·exp (jπ); ifb_(2i-1)b_(2i)=10, then phase of the current signal is shifted by 2π/3,i.e., x(i)=x(i−1)·exp (j2π/3); if b_(2i-1)b_(2i)=00, then the currentsignal remains the same, i.e., x(i)=x(i−1). In one case, θ=0. In anothercase, θ=π/4.

In one embodiment of option 5 of component X, quadrature AmplitudeModulation (QAM). QAM can be considered as an extension of PSK. In thesame way as in PSK the signal in QAM can be represented as a combinationof in-phase (I) and quadrature (Q) components, but the constellationpoints are distributed over the entire region of the constellationdiagram rather than along a circle like in PSK. In one example of QAM is16QAM modulation, where quadruplets of bits, bb₁b₂b₃, are mapped to thesymbol s=I+jQ according to TABLE 21.

TABLE 21 An example of QAM b₀b₁b₂b₃ I Q 0000  1/ {square root over (10)} 1/{square root over (10)} 0001  1/ {square root over (10)}  3/{squareroot over (10)} 0010  3/{square root over (10)}  1/{square root over(10)} 0011  3/{square root over (10)}  3/{square root over (10 )} 0100 1/{square root over (10)} −1/{square root over (10)} 0101  1/ {squareroot over (10)} −3/ {square root over (10)} 0110  3/ {square root over(10)} −1/ {square root over (10)} 0111  3/{square root over (10 )}−3/{square root over (10)} 1000 −1/{square root over (10 )}  1/{squareroot over (10)} 1001 −1/{square root over (10 )}  3/{square root over(10)} 1010 −3/{square root over (10 )}  1/{square root over (10)} 1011−3/{square root over (10 )}  3/ {square root over (10)} 1100 −1/{squareroot over (10 )} −1/{square root over (10)} 1101 −1/{square root over(10 )} −3/{square root over (10)} 1110 −3/{square root over (10 )} −1/{square root over (10)} 1111 −3/{square root over (10 )} −3/{square rootover (10)}

In another example of QAM is 64QAM modulation, where hextuplets of bits,b₀b₁b₂b₃b₄b₅, are mapped to the symbol s=I+jQ according to TABLE 22.

TABLE 22 Another example of QAM b₀b₁b₂b₃b₄b₅ I Q b₀b₁b₂b₃b₄b₅ I Q 0000003/{square root over (42)}  3/{square root over (43)} 100000 −3/{squareroot over (42)}  3/{square root over (/42)} 000001 3/{square root over(42)}  1/{square root over (42)} 100001 −3/{square root over (42)} 1/{square root over (42)} 000010 1/{square root over (42)} −1/{squareroot over (42)} 100010 −1/{square root over (42)}  3/{square root over(42)} 000011 1/{square root over (42)} −1/{square root over (42)} 100011−1/{square root over (42)}  1/{square root over (42)} 000100 3/{squareroot over (42)} −3/{square root over (42)} 100100 −3/{square root over(42)}  5/{square root over (42)} 000101 3/{square root over (42)}−1/{square root over (42)} 100101 −3/{square root over (42)}  7/{squareroot over (42)} 000110 1/{square root over (42)} −1/{square root over(42)} 100110 −1/{square root over (42)}  5/{square root over (42)}000111 1/{square root over (42)} −1/{square root over (42)} 100111−1/{square root over (42)}  7/{square root over (42)} 001000 5/{squareroot over (42)} −5/{square root over (42)} 101000 −5/{square root over(42)}  3/{square root over (42)} 001001 5/{square root over (42)}−5/{square root over (42)} 101001 −5/{square root over (42)}  1/{squareroot over (42)} 001010 7/{square root over (42)} −7/{square root over(42)} 101010 −7/{square root over (42)}  3/{square root over (42)}001011 7/{square root over (42)} −7/{square root over (42)} 101011−7/{square root over (42)}  1/{square root over (42)} 001100 5/{squareroot over (42)} −5/{square root over (42)} 101100 −5/{square root over(42)}  5/{square root over (42)} 001101 5/{square root over (42)}−5/{square root over (42)} 101101 −5/{square root over (42)}  7/{squareroot over (42)} 001110 7/{square root over (42)} −7/{square root over(42)} 101110 −7/{square root over (42)}  5/{square root over (42)}001111 7/{square root over (42)} −7/{square root over (42)} 101111−7/{square root over (42)}  7/{square root over (42)} 010000 3/{squareroot over (42)} −3/{square root over (42)} 110000 −3/{square root over(42)} −3/{square root over (42)} 010001 3/{square root over (42)}−1/{square root over (42)} 110001 −3/{square root over (42)} −1/{squareroot over (42 )} 010010 1/{square root over (42)} −3/{square root over(42)} 110010 −1/{square root over (42)} −3/{square root over (42)}010011 1/{square root over (42)} −1/{square root over (42)} 110011−1/{square root over (42)} −1/{square root over (42)} 010100 3/{squareroot over (42)} −5/{square root over (42)} 110100 −3/{square root over(42)} −5/{square root over (42)} 010101 3/{square root over (42)}−7/{square root over (42)} 110101 −3/{square root over (42)} −7/{squareroot over (42)} 010110 1/{square root over (42)} −5/{square root over(42)} 110110 −1/{square root over (42)} −5/{square root over (42)}010111 1/{square root over (42)} −7/{square root over (42)} 110111−1/{square root over (42)} −7/{square root over (42)} 011000 5/{squareroot over (42)} −3/{square root over (42)} 111000 −5/{square root over(42)} −3/{square root over (42)} 011001 5/{square root over (42)}−1/{square root over (42)} 111001 −5/{square root over (42)} −1/{squareroot over (42)} 011010 7/{square root over (42)} −3/{square root over(42)} 111010 −7/{square root over (42)} −3/{square root over (42)}011011 7/{square root over (42)} −1/{square root over (42)} 111011−7/{square root over (42)} −1/{square root over (42)} 011100 5/{squareroot over (42)} −5/{square root over (42)} 111100 −5/{square root over(42)} −5/{square root over (42)} 011101 5/{square root over (42)}−7/{square root over (42)} 111101 −5/{square root over (42)} −7/{squareroot over (42)} 011110 7/{square root over (42)} −5/{square root over(42)} 111110 −7/{square root over (42)} −5/{square root over (42)}011111 7/{square root over (42)} −7/{square root over (42)} 111111−7/{square root over (42)} −7/{square root over (42)}

In some embodiments of component XI, frequency shift keying (FSK)modulation for NR-SSS, frequency shift keying (FSK) schemes usemodulation signals with different frequencies to represent differentsets of bits. Several options of FSK for NR-SSS modulation areconsidered here, which take one or more binary bits in the input bitstream, denoted by b₀, b_(i), . . . , b_(m(i)-1) (m(i) is number of bitsmapped to one modulated symbol for codeword i, and b₀, b_(i), . . . ,b_(m(i-1)) are segment of the long sequence e₀ ^((i)), . . . ,e_(E(i)-1) ^((i)) (1707 in FIG. 17)), to output a complex-valuedmodulation symbol s=cos Φ_(k)+j sin Φ_(k), where Φ_(k)'s are initialphases for different symbols (k=1, 2, . . . , 2^(m(i)). Note that theinitial phase of modulated symbols corresponding to different binarysequence can be either the same or different. Then modulated symbols aretransmitted using different carrier frequency. For example, for k=1, 2,. . . , 2^(m(i)), the symbol s=cos Φ_(k)+j sin Φ_(k) is transmitted onusing frequency f_(c,k) (with basis functions

$ {{\Theta (t)} = {\sqrt{\frac{2}{T_{s}}}\cos \mspace{11mu} ( {2\pi f_{c,k}t} )}} ).$

In one embodiment, to facilitate coherent detection, the initial phaseof modulated symbols corresponding to different binary sequence can bethe same (Φ₁= . . . =Φ₂ _(m(i)) ), and the modulated carrier frequencyf_(c,k) is an integer multiple of ¼T_(s), and frequency spacing f_(c,k)₁ −f_(c,k) ₂ of any pair of modulated carrier frequencies f_(c,k) ₁ andf_(c,k) ₂ (k₁, k₂∈{1, 2, . . . , 2^(m(i))}) is an integer multiple of½T_(s), where T_(s) is the symbol duration of subcarriers.

The following options can be utilized for NR-SSS, where NR-SSS ismessage-based constructed. Note that the modulation schemes utilized fordifferent codewords within NR-SSS can be the same or different.

In one embodiment of component XI, coherent binary FSK (BFSK). Severalexamples of coherent BFSK modulation schemes are presented as follows.In one example for carrier frequency f_(c) with f_(s) subcarrier spacingis, Φ₁=Φ₂=0, f_(c,1)=f_(c)−( 1/12+¼N₁)f_(s), f_(c,2)=f_(c)+5/12+¼N₂)f_(s), and N₁, N₂ are integers such that f_(c,1)≠f_(c,2). Thena single bit b₀ is mapped to the two-dimensional signal space denoted as(Θ₁, Θ₂) (see TABLE 23), of basis functions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}\mspace{14mu} {and}\mspace{14mu} {\Theta_{2}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,2}t} )}.}}$

In one case, N₁=0, N₂=0. In another case, N₁=1, N₂=0. In still anothercase, N=1, N₂=1. In still another case, N₁=0, N₂=1.

TABLE 23 A single bit b₀ Vector representation in b₀ (Θ₁, Θ₂) 0 [1 0] 1[0 1]

In another example for carrier frequency f_(c) with f_(s) subcarrierspacing is, Φ₁=Φ₂=π/4, f_(c,1)=f_(c)−( 1/12+¼N₁)f_(s), f_(c,2)=f_(c)+(5/12+¼N₂)f_(s), and N₁, N₂ are integers such that f_(c,1)≠f_(c,2). Thena single bit b₀ is mapped to the two-dimensional signal space denoted as(Θ₁, Θ₂) (see TABLE 24, of basis functions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}\mspace{14mu} {and}\mspace{14mu} {\Theta_{2}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,2}t} )}.}}$

In one case, N₁=0, N₂=0. In another case, N₁=1, N₂=0. In still anothercase, N₁=1, N₂=1. In still another case, N₁=0, N₂=1.

TABLE 24 A single bit b₀ Vector representation b₀ in (Θ₁, Θ₂) 0[1/{square root over (2)} 1/{square root over (2)} ] 1 [−1/{square rootover (2)} 1/{square root over (2)} ]

In one embodiment of option 2 of component XI, coherent quadrature FSK(QFSK). Several examples of coherent QFSK modulation schemes arepresented as follows. In one example for carrier frequency f_(c) withf_(s) subcarrier spacing is, Φ₁= . . . Φ₄=0, f_(c,1)=f_(c)−(7/12+¼N₁)f_(s), f_(c,2)=f_(c)−( 1/12+¼N₂)f_(s), f_(c,3)=f_(c)+(5/12+¼N₃)f_(s), f_(c,4)=f_(c)+( 11/12+¼N₄)f_(s), and N₁, N₂, N₃, N₄ areintegers such that f_(c,1), f_(c,2), f_(c,3), f_(c,4) are different, andboth N₂−N₁ and N₄−N₃ are even. Then a single bit b₀ is mapped to thefour-dimensional signal space denoted as (Θ₁, Θ₂, Θ₃, Θ₄) (see TABLE25), of basis functions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}},{{\Theta_{2}(t)} = {\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi f_{c,2}t} )}}},{{\Theta_{3}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,3}t} )}},{{{and}\mspace{14mu} {\Theta_{4}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,4}t} )}.}}}$

In one case, N₁=0, N₂=0, N₃=0, N₄=0. In another case, N=2, N₂=0, N₃=0,N₄=2. In still another case, N₁=3, N₂=1, N₃=1, N₄=3.

TABLE 25 A single bit b₀ Vector representation in b₀b₁ (Θ₁, Θ₂, Θ₃,Θ₄)00 [1 0 0 0] 01 [0 1 0 0] 10 [0 0 1 0] 11 [0 0 0 1]

In another embodiment, to facilitate non-coherent detection, the initialphase of modulated symbols corresponding to different binary sequencecan be different (Φ_(k) are not the same) and the modulated carrierfrequency f_(c,k) is an integer multiple of ½T_(s), and frequencyspacing f_(c,k) ₁ −f_(c,k) ₂ of any pair of modulated carrierfrequencies f_(c,k) ₁ and f_(c,k) ₂ (k₁, k₂∈{1, 2, . . . , m(i)}) is aninteger multiple of 1/T_(s), where T_(s) is the symbol duration ofsubcarriers.

The following options can be utilized for NR-SSS, where NR-SSS ismessage-based constructed. Note that the modulation schemes utilized fordifferent codewords within NR-SSS can be the same or different.

In one embodiment of option 1, non-coherent Binary FSK (BFSK). Severalexamples of non-coherent BFSK modulation schemes are presented asfollows. In one example for carrier frequency f_(c) with f_(s)subcarrier spacing is, Φ₁=0, Φ₂=π, f_(c,1)=f_(c)−(⅓+½N₁)f_(s),f_(c,2)=f_(c)+(⅔+⅓N₂)f_(s), and N₁, N₂ are integers such thatf_(c,1)≠f_(c,2). Then a single bit b₀ is mapped to the two-dimensionalsignal space denoted as (Θ₁, Θ₂) (see TABLE 26), of basis functions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}\mspace{14mu} {and}\mspace{14mu} {\Theta_{2}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,2}t} )}.}}$

In one case, N₁=0, N₂=0. In another case, N₁=1, N₂=0. In still anothercase, N=1, N₂=1. In still another case, N₁=0, N₂=1.

TABLE 26 A single bit b₀ Vector representation in b₀ (Θ₁, Θ₂) 0 [1 0] 1[−1 0]

In another example for carrier frequency f_(c) with f_(s) subcarrierspacing is, Φ₁=π/4, Φ₂=5π/4, f_(c,1)=f_(c)−(⅓+½N₁)f_(s),f_(c,2)=f_(c)+(⅔+½N₂)f_(s), and N₁, N₂ are integers such thatf_(c,1)≠f_(c,2). Then a single bit b₀ is mapped to the two-dimensionalsignal space denoted as (Θ₁, Θ₂) (see TABLE 27), of basis functions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}\mspace{14mu} {and}\mspace{14mu} {\Theta_{2}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,2}t} )}.}}$

In one case, N₁=0, N₂=0. In another case, N₁=1, N₂=0. In still anothercase, N₁−1, N₂=1. In still another case, N₁=0, N₂=1.

TABLE 27 A single bit b₀ Vector representation in b₀ (Θ₁, Θ₂) 0[1/{square root over (2)} 1/{square root over (2)} ] 1 [−1/{square rootover (2)} −1/{square root over (2)} ]

In one embodiment of option 2, non-coherent quadrature FSK (QFSK).Several examples of non-coherent QFSK modulation schemes are presentedas follows. In one example for carrier frequency f_(c) with f_(s)subcarrier spacing is, Φ₁=Φ₂=0, Φ₃=Φ₄=π, f_(c,1)=f_(c)−(4/3+½N)f_(s),f_(c,2)=f_(c)−(⅓+½N₂)f_(s), f_(c,3)=f_(c)+(⅔+½N₃)f_(s),f_(c,4)=f_(c)+(5/3+½N₄)f_(s), and N₁, N₂, N₃, N₄ are integers such thatf_(c,1), f_(c,2), f_(c,3), f_(c,4) are different, and both N₂−N₁ andN₄−N₃ are even. Then a single bit b₀ is mapped to the four-dimensionalsignal space denoted as (Θ₁, Θ₂, Θ₃, Θ₄) (see TABLE 28), of basisfunctions

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}},{{\Theta_{2}(t)} = {\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi f_{c,2}t} )}}},{{\Theta_{3}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,3}t} )}},{{{and}\mspace{14mu} {\Theta_{4}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,4}t} )}.}}}$

In one case, N₁=0, N₂=0, N₃=0, N₄=0. In another case, N=2, N₂=0, N₃=0,N₄=2. In still another case, N₁=3, N₂=1, N₃=1, N₄=3.

TABLE 28 Bit b₀b₁ Vector representation in b₀b₁ (Θ₁, Θ₂, Θ₃, Θ₄) 00 [1 00 0] 01 [0 1 0 0] 10 [0 0 −1 0] 11 [0 0 0 −1]

In another example for carrier frequency f_(c) with f_(s) subcarrierspacing is, Φ₁=Φ₂=π/4, Φ₃=Φ₄=5π/4, f_(c,1)=f_(c)−(4/3+½N₁)f_(s),f_(c,2)=f_(c)−(⅓+½N₂)f_(s), f_(c,3)=f_(c)+(⅔+½N₃)f_(s),f_(c,4)=f_(c)+(5/3+½N₄)f_(s), and N₁, N₂, N₃, N₄ are integers such thatf_(c,1), f_(c,2), f_(c,3), f_(c,4) are different, and both N₂−N₁ andN₄−N₃ are even. Then a single bit b₀ is mapped to the four-dimensionalsignal space denoted as (Θ₁, Θ₂, Θ₃, Θ₄) (see TABLE 29), of basisfunctions,

${{\Theta_{1}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,1}} )}},{{\Theta_{2}(t)} = {\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi f_{c,2}t} )}}},{{\Theta_{3}(t)}\sqrt{\frac{2}{T_{s}}}{\cos ( {2\pi \; f_{c,3}t} )}},{{{and}\mspace{14mu} {\Theta_{4}(t)}} = {\sqrt{\frac{2}{T_{s}}}{{\cos ( {2\pi f_{c,4}t} )}.}}}$

In one case, N₁=0, N₂=0, N₃=0, N₄=0. In another case, N=2, N₂=0, N₃=0,N₄=2. In still another case, N₁=3, N₂=1, N₃=1, N₄=3.

TABLE 29 Bit b₀b₁ Vector representation in b₀b₁ (Θ₁, Θ₂, Θ₃, Θ₄) 00[1/{square root over (2)}, 1/{square root over (2)} 0 0] 01 [0 1/{squareroot over (2)} 1/{square root over (2)} 0] 10 [0 0 −1/{square root over(2)} −1/{square root over (2)}] 11 [1/{square root over (2)} 0 0−1/{square root over (2)} ]

In some embodiments of component XII, amplitude shift keying (ASK)modulation for NR-SSS, amplitude shift keying (ASK) schemes usemodulation signals with different amplitudes to represent different setsof bits. Several options of ASK for NR-SSS modulation are consideredhere, which take one or more binary bits in the input bit stream,denoted by b₀, b_(i), . . . , b_(m(i-1))(m(i) is number of bits mappedto one modulated symbol for codeword i, and b₀, b_(i), . . . ,b_(m(i-1)) are segment of the long sequence e₀ ^((i)), . . . ,e_(E(i)-1) ^((i)) (1707 in FIG. 17)), to output a complex-valuedmodulation symbol s=I+jQ, where I (inphase component) and Q (quadraturecomponent) are real numbers.

The following options can be utilized for NR-SSS, where NR-SSS ismessage-based constructed. Note that the modulation schemes utilized fordifferent codewords within NR-SSS can be the same or different.

In one embodiment of option 1, on-off keying (OOK). In case of OOKmodulation, a single bit b₀ is mapped to the symbol s=I+jQ according toTABLE 30. This is a version of non-coherent ASK.

TABLE 30 A single bit b₀ b₀ I Q 0 0 0 1 {square root over (2)} 0

Although the present disclosure has been described with an exemplaryembodiment, various changes and modifications may be suggested to oneskilled in the art. It is intended that the present disclosure encompasssuch changes and modifications as fall within the scope of the appendedclaims.

None of the description in this application should be read as implyingthat any particular element, step, or function is an essential elementthat must be included in the claims scope. The scope of patented subjectmatter is defined only by the claims. Moreover, none of the claims areintended to invoke 35 U.S.C. § 112(f) unless the exact words “means for”are followed by a participle.

What is claimed is:
 1. Abase station for transmitting synchronizationsignals in a wireless communication system, the base station comprising:at least one processor configured to: obtain a primary synchronizationsignal (PSS) including one PSS sequence that is associated with a firstsequence of length 127, wherein a part of physical cell identification(ID) information is indicated by the one PSS sequence, wherein the onePSS sequence is mapped on to consecutive subcarriers in one OFDM symbol,and obtain a secondary synchronization signal (SSS) including one SSSsequence that is defined by combination between a second sequence and athird sequence of length 127, wherein the physical cell ID informationis indicated by the SSS sequence; and a transceiver configured totransmit, to a user equipment (UE), the PSS and the SSS over a frequencyposition for the PSS and the SSS, wherein the PSS is place ontodifferent OFDM symbol from the SSS and a physical broadcast channel(PBCH), wherein the PSS and the SSS are placed on only a part ofresource elements available for the PBCH, and wherein a bandwidth forthe PSS is same as a bandwidth for the SSS.
 2. The base station of claim1, wherein the second sequence and the third sequence are M-sequences.3. The base station of claim 1, wherein the PSS is applicable for allfrequency band associated with new radio (NR).
 4. The base station ofclaim 1, wherein a size of a frequency band for the PSS is proportionalto a size of subcarrier spacing.
 5. The base station of claim 1, whereinPSS sequence is defined based on a first cyclic shift of the firstsequence, wherein the part of physical cell ID information is indicatedby the first cyclic shift, wherein SSS sequence is defined based on asecond cyclic shift of the second sequence and a third cyclic shift ofthe third cyclic shift, wherein the physical cell ID information isindicated by at least one of the second cyclic shift and the thirdcyclic shift, and wherein the first sequence and the second sequence aredefined by same polynomial.
 6. A method for transmitting synchronizationsignals performed by a base station in a wireless communication system,the method comprising: obtaining a primary synchronization signal (PSS)including one PSS sequence that is associated with a first sequence oflength 127, wherein a part of physical cell identification (ID)information is indicated by the one PSS sequence, wherein the one PSSsequence is mapped on to consecutive subcarriers in one OFDM symbol;obtaining a secondary synchronization signal (SSS) including one SSSsequence that is defined by combination between a second sequence and athird sequence of length 127, wherein the physical cell ID informationis indicated by the SSS sequence; and transmitting, to a user equipment(UE), the PSS and the SSS over a frequency position for the PSS and theSSS, wherein the PSS is place onto different OFDM symbol from the SSSand a physical broadcast channel (PBCH), wherein the PSS and the SSS areplaced on only a part of resource elements available for the PBCH, andwherein a bandwidth for the PSS is same as a bandwidth for the SSS. 7.The method of claim 6, wherein the second sequence and the thirdsequence are M-sequences.
 8. The method of claim 6, wherein the PSS isapplicable for all frequency band associated with new radio (NR).
 9. Themethod of claim 6, wherein a size of a frequency band for the PSS isproportional to a size of subcarrier spacing.
 10. The method of claim 6,wherein PSS sequence is defined based on a first cyclic shift of thefirst sequence, wherein the part of physical cell ID information isindicated by the first cyclic shift, wherein SSS sequence is definedbased on a second cyclic shift of the second sequence and a third cyclicshift of the third cyclic shift, wherein the physical cell IDinformation is indicated by at least one of the second cyclic shift andthe third cyclic shift, and wherein the first sequence and the secondsequence are defined by same polynomial.
 11. A user equipment (UE) forreceiving synchronization signals in a wireless communication system,the UE comprising: a transceiver configured to receive, from a basestation, a primary synchronization signal (PSS) and a secondarysynchronization signal (SSS) over a frequency position for the PSS andthe SSS; and at least one processor coupled with the transceiver andconfigured to: identify the PSS including one PSS sequence that isassociated with a first sequence of length 127, wherein a part ofphysical cell identification (ID) information is indicated by the onePSS sequence, wherein the one PSS sequence is mapped on to consecutivesubcarriers in one OFDM symbol, and identify the SSS including one SSSsequence that is defined by combination between a second sequence and athird sequence of length 127, wherein the physical cell ID informationis indicated by the SSS sequence, wherein the PSS is place ontodifferent OFDM symbol from the SSS and a physical broadcast channel(PBCH), wherein the PSS and the SSS are placed on only a part ofresource elements available for the PBCH, and wherein a bandwidth forthe PSS is same as a bandwidth for the SSS.
 12. The UE of claim 11,wherein the second sequence and the third sequence are M-sequences. 13.The UE of claim 11, wherein the PSS is applicable for all frequency bandassociated with new radio (NR).
 14. The UE of claim 11, wherein a sizeof a frequency band for the PSS is proportional to a size of subcarrierspacing.
 15. The UE of claim 11, wherein PSS sequence is defined basedon a first cyclic shift of the first sequence, wherein the part ofphysical cell ID information is indicated by the first cyclic shift,wherein SSS sequence is defined based on a second cyclic shift of thesecond sequence and a third cyclic shift of the third cyclic shift,wherein the physical cell ID information is indicated by at least one ofthe second cyclic shift and the third cyclic shift, and wherein thefirst sequence and the second sequence are defined by same polynomial.16. A method for receiving synchronization signals performed by a userequipment (UE) in a wireless communication system, the methodcomprising: receiving, from a base station, a primary synchronizationsignal (PSS) and a secondary synchronization signal (SSS) over afrequency position for the PSS and the SSS; identifying the PSSincluding one PSS sequence that is associated with a first sequence oflength 127, wherein a part of physical cell identification (ID)information is indicated by the one PSS sequence, wherein the one PSSsequence is mapped on to consecutive subcarriers in one OFDM symbol; andidentifying the SSS including one SSS sequence that is defined bycombination between a second sequence and a third sequence of length127, wherein the physical cell ID information is indicated by the SSSsequence, wherein the PSS is place onto different OFDM symbol from theSSS and a physical broadcast channel (PBCH), wherein the PSS and the SSSare placed on only a part of resource elements available for the PBCH,and wherein a bandwidth for the PSS is same as a bandwidth for the SSS.17. The method of claim 16, wherein the second sequence and the thirdsequence are M-sequences.
 18. The method of claim 16, wherein the PSS isapplicable for all frequency band associated with new radio (NR). 19.The method of claim 16, wherein a size of a frequency band for the PSSis proportional to a size of subcarrier spacing.
 20. The method of claim16, wherein PSS sequence is defined based on a first cyclic shift of thefirst sequence, wherein the part of physical cell ID information isindicated by the first cyclic shift, wherein SSS sequence is definedbased on a second cyclic shift of the second sequence and a third cyclicshift of the third cyclic shift, wherein the physical cell IDinformation is indicated by at least one of the second cyclic shift andthe third cyclic shift, and wherein the first sequence and the secondsequence are defined by same polynomial.